1. Field of the Invention
The present invention relates in general to the field of electronics, and more specifically to a system and method for sensing switch controlled currents using a Hall effect sensor.
2. Description of the Related Art
Electronic systems often detect signal values and utilize the values to perform other operations. Hall effect sensors (“Hall sensors”) are used in some contexts to detect signals. A Hall sensor generates a voltage corresponding to a magnetic field passing through the Hall sensor. An electrical current flowing through a conductor in proximity to a Hall sensor generates a magnetic field. The Hall sensor generates a voltage corresponding to the magnetic field generated by the current. Hall sensors generally have a low frequency noise component that is too large to allow detection of small changes in currents. For example, as explained subsequently in more detail, switching power converters that operate in continuous conduction mode (CCM) sense currents using a current sense circuit such as a resistor or a transformer.
The switching power converter 102 includes at least two switching operations, i.e. controlling field effect transistor (FET) 108 to provide power factor correction and controlling FET 108 to provide regulation of link voltage VLINK. The goal of power factor correction technology is to make the switching power converter 102 appear resistive to the voltage source 101 so that the real power provided to switching power converter 102 is equal to the apparent power provided to switching power converter 102. The inductor current iL ramps ‘up’ when FET 108 conducts, i.e. is “ON”. The inductor current iL ramps down when FET 108 is nonconductive, i.e. is “OFF”, and supplies current iL to recharge capacitor 106. The time period during which inductor current iL ramps down is commonly referred to as the “inductor flyback time”. Diode 111 prevents reverse current flow into inductor 110. In at least one embodiment, control signal CS0 is a pulse width modulated signal, and FET 108 is an n-channel FET. In this embodiment, control signal CS0 is a gate voltage of FET 108, and FET 108 conducts when the pulse width of CS0 is high. Thus, the ‘on-time’ of FET 108 is determined by the pulse width of control signal CS0. In at least one embodiment, the switching power converter 102 operates in CCM, i.e. ramp up time of the inductor current iL plus the inductor flyback time is greater than or equal to the period of the control signal CS0.
In at least one embodiment, switching power converter 102 boosts a 110-120 V rectified input voltage VX to a higher link voltage VLINK, such as 200-400V. Accordingly, FET 108 is fabricated to have a breakdown voltage sufficient to accommodate the controlled current iCCT and voltage drops across FET 108 associated with the high input voltage VX and higher link voltage VLINK. FET 108 is a high breakdown voltage device fabricated using a “high” voltage process. In at least one embodiment, FET 108 has a breakdown voltage greater than or equal to 30V and at least sufficient to accommodate operating characteristics of switching power converter 102. In at least one embodiment, power factor correction (PFC) and output voltage controller 114 is an integrated circuit and is fabricated using a low voltage process that is insufficient to fabricate a switch with a sufficiently high breakdown voltage to control the controlled current iCCT. Thus, FET 108 is located external to PFC and output voltage controller 114. As subsequently described in more detail, PFC and output voltage controller 114 generates a pulse width modulated control signal CS0 to control conductivity of FET 108. In at least one embodiment, FET 108 is a FET, and control signal CS0 is a gate voltage.
Switching power converter 102 includes current sense resistor 109. The switch controlled current iCC generates a sense voltage VSEN across current sense resistor 109. The PFC and output voltage controller 114 receives the sense voltage VSEN. The resistance R of sense resistor 109 is known. The sense voltage VSEN is directly related to switch controlled current iCC via Ohm's law, i.e. VSEN=iCC·R. “R” represents a resistance value of sense resistor 109, and the value of R is a matter of design choice. In at least one embodiment, PFC and output voltage controller 114 utilizes the sense voltage VSEN and sensing two signals, namely, the line input voltage VX and the capacitor voltage/output voltage VLINK to generate the pulse width and duty cycle of control signal CS0.
Capacitor 106 supplies stored energy to load 112. The capacitor 106 is sufficiently large so as to maintain a substantially constant output voltage VLINK, as established by PFC and output voltage controller 114 (as discussed in more detail below). The output voltage VLINK remains substantially constant during constant load conditions. However, as load conditions change, the output voltage VLINK changes. The switch state controller 114 responds to the changes in VLINK and adjusts the control signal CS0 to restore a substantially constant output voltage as quickly as possible. The PFC and output voltage controller 114 includes a small capacitor 115 to filter any high frequency signals from the line input voltage VX.
The switch state controller 114 of power control system 100 controls FET 108 and, thus, controls power factor correction (PFC) and regulates output power of the switching power converter 102. As previously stated, the goal of power factor correction technology is to make the switching power converter 102 appear resistive to the voltage source 101. Thus, the switch state controller 114 attempts to control the inductor current iL so that the average inductor current iL is linearly and directly related to the line input voltage VX. A CCM PFC controller, model number UCC28019A, available from Texas Instruments, Inc., Texas, USA is an example of switch state controller 114. The switch state controller 114 controls the pulse width (PW) and period (TT) of control signal CS0. To regulate the amount of energy transferred and maintain a power factor close to one, switch state controller 114 varies the period of control signal CS0 so that the input current iL tracks the changes in input voltage VX and holds the output voltage VLINK constant. Thus, as the input voltage VX increases, switch state controller 114 increases the period TT of control signal CS0, and as the input voltage VX decreases, switch state controller 114 decreases the period of control signal CS0. At the same time, the pulse width PW of control signal CS0 is adjusted to maintain a constant duty cycle (D) of control signal CS0, and, thus, hold the output voltage VLINK constant.
In at least one embodiment, the switch state controller 114 updates the control signal CS0 at a frequency much greater than the frequency of input voltage VX. The frequency of input voltage VX is generally 50-60 Hz. The frequency 1/TT of control signal CS0 is, for example, between 20 kHz and 130 kHz. Frequencies at or above 20 kHz avoid audio frequencies and frequencies at or below 130 kHz avoid significant switching inefficiencies while still maintaining good power factor, e.g. between 0.9 and 1, and an approximately constant output voltage VLINK.
Light emitting diodes (LEDs) are becoming particularly attractive as main stream light sources in part because of energy savings through high efficiency light output and environmental incentives such as the reduction of mercury. LEDs are semiconductor devices and are driven by direct current. The brightness (i.e. luminous intensity) of the LED approximately varies in direct proportion to the current flowing through the LED. Thus, increasing current supplied to an LED increases the brightness of the LED and decreasing current supplied to the LED dims the LED. Current can be modified by either directly reducing the direct current level to the LEDs or by reducing the average current through the LEDs through duty cycle modulation.
The controller 156 is, for example, a Supertex HV9915B integrated circuit controller available from Supertex, Inc. of Sunnyvale, Calif. The link voltage VLINK can vary from, for example, 8V to 450V. The controller 156 provides a gate drive signal from the GATE output node to the n-channel metal oxide semiconductor field effect transistor (MOSFET) Q1. Controller 156 modulates the gate drive signal, and thus, the conductivity of MOSFET Q1 to provide a constant current to LED system 154. Controller 156 modifies the average resistance of MOSFET Q1 by varying a duty cycle of a pulse width modulated gate drive signal VGATE. Resistor R1 and capacitor C3 provide external connections for controller 156 to the ground reference.
Controller 156 generates and uses feedback to maintain a constant current iLED for LEDs 158. Controller 156 receives a current feedback signal Vfb representing a feedback voltage Vfb sensed across sense resistor R2. The feedback voltage Vfb is directly proportional to the LED current iLED in LEDs 158. If the feedback voltage Vfb exceeds a predetermined reference corresponding to a desired LED current, the controller 156 responds to the feedback voltage Vfb by decreasing the duty cycle of gate drive signal VGATE to increase the average resistance of MOSFET Q1 over time. If the feedback voltage Vfb is less than a predetermined reference corresponding to the desired LED current, the controller 156 responds to the feedback voltage Vfb by increasing the duty cycle of gate drive signal VGATE to decrease the average resistance of MOSFET Q1 over time.
The LED system 154 includes a chain of one or more, serially connected LEDs 158. When the MOSFET Q1 is “on”, i.e. conductive, diode D1 is reversed bias and, current iLED flows through the LEDs 158 and charges inductor L1. When the MOSFET Q1 is “off”, i.e. nonconductive, the voltage across inductor L1 changes polarity, and diode D1 creates a current path for the LED current iLED. The inductor L1 is chosen so as to store enough energy to maintain a constant current iLED when MOSFET Q1 is “off”.
Sensing the controlled current through current sense circuit 109 (
In one embodiment of the present invention, an apparatus includes an integrated circuit. The integrated circuit includes a Hall sensor configured to sense a magnetic field of a controlled current. The integrated circuit also includes a controller coupled to the Hall sensor, wherein the controller is configured to receive information from the Hall sensor and to use the information to determine a time to cause a switch, which controls the controlled current, to conduct.
In another embodiment of the present invention, a method includes sensing a magnetic field of a controlled current using a Hall sensor and receiving information from the Hall sensor. The method further includes utilizing the information to determine a time to cause a switch, which controls the controlled current, to conduct.
In a further embodiment of the present invention, an apparatus includes means for sensing a magnetic field of a controlled current using a Hall sensor. The apparatus also includes means for receiving information from the Hall sensor, and means for utilizing the information to determine a time to cause a switch, which controls the controlled current, to conduct.
The present invention may be better understood, and its numerous objects, features and advantages made apparent to those skilled in the art by referencing the accompanying drawings. The use of the same reference number throughout the several figures designates a like or similar element.
An electronic system includes a Hall sensor to sense a magnetic field of a controlled current. An average value of the current is controlled by controlling a switch. In at least one embodiment, a controller generates a duty cycle modulated switch control signal to control the switch. Increasing the duty cycle of the switch control signal increases the average value of the controlled current, and decreasing the duty cycle decreases the average value of the controlled current. The controller utilizes information from the Hall sensor about the magnetic field of the controlled current as feedback to control the controlled current. For example, if the information from the Hall sensor indicates the controlled current is too high relative to a target value, the controller decreases the duty cycle of the switch control signal. If the information from the Hall sensor indicates the controlled current is too low relative to the target value, the controller increases the duty cycle of the switch control signal.
In general, conventionally, low frequency noise of a Hall sensor prevents the Hall sensor from accurately sensing voltages related to small changes in current. In a switching power converter, in at least one embodiment, an average current in the switching power converter is controlled within +/−a few milliamps. Thus, conventionally, Hall sensors are not used in such applications because of the relatively large noise component of the Hall sensor. In at least one embodiment, a switching frequency fiCCT of the switch in the switching power converter corresponds to a frequency of pulses of the controlled current. The switching frequency fiCCT of the switch and, thus, the frequency of the controlled current is high relative to a frequency fN of the noise of the Hall sensor. For example, in at least one embodiment, fiCCT is at least 100 times larger than the noise frequency, i.e. fiCCT≧100·fN. Because fiCCT>>fN, the Hall noise voltage is effectively constant during a single cycle of the controlled current. The controller can determine a difference between information from the Hall sensor that does not include a component associated with the controlled current to information that includes a component associated with the controlled current and effectively cancel out the Hall sensor noise since the Hall noise voltage is effectively constant during a pulse of the controlled current. For example, if while the Hall noise voltage is effectively constant, the information that does not include a component associated with the controlled current is a baseline voltage VHB and the information that includes the component associated with the controlled current is VHB+VICCT, then the controller can determine ViCCT by subtraction, i.e. ViCCT=VHB−(VHB+ViCCT). “ViCCT” corresponds to a value of the controlled current. The controller can, thus, effectively cancel out the noise from the Hall sensor. The controller can then utilize the determined value ViCCT of the controlled current as feedback to generate the switch control signal to control the controlled current.
In at least one embodiment, the Hall sensor is positioned proximate to a signal path that conducts the controlled current and develops a voltage that includes a voltage component corresponding to the controlled current. A controller controls conductivity of a switch, and the switch controls the controlled current. Controlling conductivity of the switch controls the controlled current. The controller receives information either directly or indirectly from the Hall sensor corresponding to the controlled current and utilizes the information from the Hall sensor to control conductivity of the switch. In at least one embodiment, the controller generates a duty cycle modulated control signal to control the switch. In at least one embodiment, a pulse of the control signal causes the switch to turn “on”, i.e. conduct. In at least one embodiment, the switch can control the current for any purpose, including but not limited to providing power factor correction in a switching power converter and/or driving a load. The load can be any type of load including but not limited to, for example, a light emitting diode (LED) based light source.
In at least one embodiment, the electronic system includes a switching power converter operating in continuous conduction mode (CCM). The Hall sensor senses a magnetic field generated by a controlled current in the switch of the switching power converter and generates a sense signal corresponding to the controlled current. The controller utilizes the sense signal to provide, for example, power factor correction for the CCM switching power converter. In at least one embodiment, the switching power converter operates in discontinuous conduction mode (DCM), and the controller utilizes the sense signal to provide, for example, power factor correction for the DCM switching power converter.
In at least one embodiment, the electronic system includes a light source having one or more light emitting diodes (LEDs). The Hall sensor senses a magnetic field generated by a controlled current in the LEDs and generates a sense signal corresponding to the controlled current. The controller utilizes the sense signal to regulate current in the LEDs.
In at least one embodiment, the Hall sensor and the controller are at least part of an integrated circuit that is connected to a printed circuit board. The printed circuit board includes a signal path, referred to as a “signal trace”, that conducts the controlled current. In at least one embodiment, the Hall sensor is positioned proximate to the signal trace and develops a voltage that includes a voltage component corresponding to the controlled current.
In at least one embodiment, utilizing the Hall sensor to detect the controlled current iCCT is more accurate than using a sense resistor (such as sense resistor 109 (
Electronic system 200 also includes a power source 208 to supply the controlled current iCCT to load 210. Power source 208 can be any source of power, such as voltage source 101 or any power supply that supplies enough power for operation of load 210. Load 210 can be any type of load that utilizes or supplies a switch controlled current iCCT. In at least one embodiment, load 210 includes one or more light emitting diodes (LEDs).
Controller 202 generates switch control signal CS1 to control conductivity of current control switch 204 using, for example, duty cycle modulation. Switch 204 can be any type of switch that can be controlled by a switch control signal. In at least one embodiment, switch 204 is a field effect transistor (FET), and switch control signal CS1 is a duty cycle modulated signal. In at least one embodiment, each pulse 212 of control signal CS1 causes switch 204 to conduct. When each pulse ends, switch 204 is nonconductive. Turning switch 204 “on” and “off” in accordance with the duty cycle of switch control signal CS1 establishes an average resistance of switch 204. Since an average value of controlled current iCCT is directly related to the average resistance of switch 204, the duty cycle of control signal CS1 controls an average value of controlled current iCCT.
The Hall sensor 203 generates a voltage corresponding to a magnetic field of controlled current iCCT. Hall sensor 203 also produces a noise voltage component that can represent a significant component of the voltage generated by Hall sensor 203. In at least one embodiment, the noise voltage of Hall sensor 203 has a relatively low frequency fN relative to a frequency fiCCT of switch control signal CS1. In at least one embodiment, the frequency fiCCT of switch control signal CS1 is also the frequency of controlled current iCCT. As illustratively described in more detail below, in at least one embodiment, because fiCCT>>fN, controller 202 can sense a baseline noise voltage VHB of Hall sensor 203 (or obtain a representation of the baseline voltage VHB, such as an amplified baseline voltage VHB) prior to sensing a signal voltage corresponding to the magnetic field of controlled current iCCT. In at least one embodiment, the frequency fiCCT is 100-1,000 times greater than the noise frequency fN. The frequency fiCCT of switch control signal CS1 is a matter of design choice. In at least one embodiment, since the baseline noise voltage VHB remains effectively constant during a pulse of the higher frequency controlled current, controller 202 subsequently determines the voltage VICCT corresponding to the magnetic field of the controlled current iCCT by subtracting the baseline noise VHB voltage of Hall sensor 203 from a Hall sensor output voltage VH representing VICCT and VHB. Thus, controller 202 effectively cancels out the baseline noise voltage VHB of Hall sensor 203. Since the controlled current iCCT corresponds to the voltage VICCT corresponding to the magnetic field of the controlled current iCCT, controller 202 can determine a value of the controlled current iCCT. The dashed A-A line is a cross-section reference for controller 202 discussed subsequently with reference to
Controller 242 generates control signal CS2 to control conductivity of current control switch 244. Switch 244 can be any type of switch that can be controlled by a switch control signal. In at least one embodiment, switch 244 is a field effect transistor (FET), and switch control signal CS2 is a duty cycle modulated signal. In at least one embodiment, each pulse 214 of control signal CS2 causes switch 244 to conduct. When each pulse ends, switch 244 is nonconductive. Thus, the duty cycle of control signal CS2 controls an average value of controlled current iCCT through switch 244. The particular methodology for generating control signal CS2 using feedback from Hall sensor 203 is a matter of design choice.
Electronic system 240 also includes a voltage source 246 to provide a supply voltage to switching power converter 248. In at least one embodiment, voltage source 246 is a public utility voltage source such as voltage supply 101 (
Load driver 278 can be any type of load driver that provides a controlled current iCCT to load 280. In at least one embodiment, load driver 278 is a switching power converter, such as switching power converter 248, and controller 272 also generates a switch control signal CS2 to control switch 244 as described with reference to
Controller 272 generates control signal CS1 to control conductivity of a current control switch 274. Switch 274 can be any type of switch that can be controlled by a switch control signal. In at least one embodiment, switch 274 is a field effect transistor (FET), and switch control signal CS2 is a duty cycle modulated signal. In at least one embodiment, each pulse 284 of control signal CS2 causes switch 274 to conduct. When each pulse ends, switch 274 is nonconductive. Thus, the duty cycle of control signal CS2 controls an average value of controlled current iCCT. The generation of control signal CS2 is a matter of design choice. In at least one embodiment, controller 272 generates switch control signal CS2 in the manner of generating a switch control signal illustratively described in U.S. patent application Ser. No. 11/864,366, entitled “Time-Based Control of a System having Integration Response,” inventor John L. Melanson, and filed on Sep. 28, 2007 (referred to herein as “Melanson I”). In at least one embodiment, controller 272 generates switch control signal CS2 in the manner of generating a switch control signal illustratively described in U.S. patent application Ser. No. 12/415,830, entitled “Primary-Side Based Control Of Secondary-Side Current For An Isolation Transformer,” inventor John L. Melanson, and filed on Mar. 31, 2009 (referred to herein as “Melanson II”). Melanson I and II are incorporated by reference in their entireties.
As similarly described with reference to electronic system 200 (
Because the Hall sensor 203 functions based upon a magnetic field of controlled current iCCT, the discussion no references
An exemplary operation of controller 300 is described with reference to
Hall sensor 302 is an example of a Hall effect device. The particular design of Hall sensor 302 is a matter of design choice. Hall sensor 302 is, for example, fabricated from conductive material in a layer as part of an integrated circuit version of controller 300. In some embodiments, Hall sensor 302 is a silicon diffusion layer, a doped silicon layer, or polysilicon. Hall sensor 302 has four connection tabs 304, 306, 308, and 310. Tab 304 is connected to a constant current source 311, and tab 308 is connected to a reference, such as ground. Constant current source 311 supplies a current iH that flows through Hall sensor 302. As controlled current iCCT flows through signal path 612, a magnetic field B develops through the Hall sensor 302 as illustratively discussed in conjunction with
In at least one embodiment, signal path 612 has one turn as depicted in cross-section in
Routing of the signal path conducting controlled current iCCT is a matter of design choice. The signal path 612
Referring to
Referring now to
In operation 404, processor 318 generates a pulse of control signal CS1 at time t1, which causes switch 322 to conduct and the controlled current iCCT to increase. The particular methodology for generating control signal CS1 is a matter of design choice. In at least one embodiment, each period of control signal CS1 is constant, as, for example, described in Melanson I and II (“periods” are described in terms of switch states in Melanson I).
The time lapse between times t0 and t1 is a matter of design choice. In at least one embodiment, the time lapse between times t1−t0 is minimized to establish a baseline noise voltage VHB that is approximately unchanged between times t0 and t2. In operation 406, processor 318 samples the Hall sensor output voltage VH at time t1 to determine an initial voltage value V0 of the Hall sensor voltage Hall sensor output voltage VH. The initial value V0 represents the Hall baseline noise voltage VHB plus the voltage VICCT corresponding to the controlled current iCCT at the beginning of the pulse of switch control signal CS1. The initial value of the controlled current iCCT at time t1 is a function of V0−VHB, since V0=VHB+VICCT. As previously discussed, determination of the initial value of the controlled current iCCT from V0−VHB is a well-known function based on the material make-up of the Hall sensor 203, the number of turns of signal path 206, and distances d0, d1, and d2 (
As the controlled current iCCT increases, the strength of the magnetic field B increases, and, thus, the voltage VICCT component of the Hall sensor output voltage VH also increases as shown by arrow 506. However, since the noise frequency fN of Hall sensor 304 is much less than the frequency fiCCT of the switch control signal CS1, the baseline noise voltage VHB remains relatively constant during period TA. Processor 318 continues to sample the Hall sensor output voltage VH to determine when the Hall sensor output voltage VH has increased from the initial voltage V0 to the target voltage VTARGET. The particular sampling frequency of the Hall sensor output voltage VH is a matter of design choice. In at least one embodiment, the sampling frequency is high enough to determine approximately when the Hall sensor output voltage VH has increased from the initial voltage V0 to the target voltage VTARGET.
Operation 408 determines whether the Hall sensor output voltage VH has increased from the initial voltage V0 by a target voltage VTARGET. In at least one embodiment, the target voltage VTARGET is directly related to the controlled current iCCT. The particular target voltage VTARGET depends on, for example, a desired average controlled current. For example, in at least one embodiment, the initial voltage V0 represents 350 mA, the target voltage VTARGET represents 50 mA, and the peak voltage V1 represents 400 mA, so that the average controlled current equals 400 mA.
In at least one embodiment, to determine if the Hall sensor output voltage VH equals the initial voltage V0+VTARGET, between times t1 and t2 operation 408 subtracts the initial voltage V0 from a sampled Hall sensor output voltage VH to determine if the sampled Hall sensor output voltage VH has increased from the initial voltage V0 by an amount equal to the target voltage VTARGET. The frequency fiCCT of switch control signal CS1 is large relative to the frequency fN of Hall voltage noise 502. For example, in at least one embodiment, the frequency of switch control signal CS1 is approximately 100 kHz, and the frequency of the Hall voltage noise 502 is approximately 100 Hz. So, the Hall voltage noise 502 remains approximately constant between times t1 and t3. Thus, subtracting the initial sampled Hall sensor voltage V0 corresponding to the leading edge of switch control signal CS1 at time t1 from the current sample of Hall sensor output voltage VH represents the change VΔ in the voltage VICCT corresponding to the controlled current iCCT, i.e. VH=V0+VΔ.
If the Hall sensor output voltage VH does not equal the initial voltage V0+VTARGET, in operation 410, processor 318 continues generating a pulse of switch control signal CS1 to keep switch 322 “on”. Thus, the controlled current iCCT continues to increase causing the Hall sensor output voltage VH to increase. Operation 410 returns to operation 408, and processor 318 continues to sense the Hall sensor output voltage VH. If in operation 408 processor 318 determines that VΔ=VTARGET, operation 412 determines the time t2 at which VΔ=VTARGET.
In operation 414, processor 318 determines the time t3 at which to cease generating the pulse of control signal CS1 and, thus, turn switch 322 “off”. In at least one embodiment, the switch 322 turn “off” time t3 is set so that times t3−t2=t2−t1. Time period TA equals times t2−t1, and time period TB equals times t3−t2. Thus, in at least one embodiment, processor 318 sets the time period TA during which the Hall sensor output voltage VH rises from the baseline voltage V0 to the target voltage VTARGET V0 to be the same or approximately the same as the time period TB during which the Hall sensor output voltage VH rises from the target voltage VTARGET+V0 to a peak voltage V1.
In operation 416, processor 318 ends the pulse of control signal Cs1, thus, turning switch 322 “off”. When switch 322 is “off”, the controlled current iCCT continues to decrease. Operation 402 restarts controlled current detection and switch control algorithm 400 at the beginning of period TT1 for control signal CS1 and continues for each consecutive period.
As previously discussed, the connection and routing of signal paths 206, 265, and 312, which conduct embodiments of the controlled current iCCT, are a matter of design choice.
Referring to
Referring to
The routings, connections, and configurations of a signal path to allow Hall sensor 203 to sense the magnetic field generated by the controlled current iCCT are virtually limitless and are a matter of design choice.
Thus, an electronic system includes a Hall sensor to sense a controlled current, and a controller receives information either directly or indirectly from the Hall sensor corresponding to the controlled current and utilizes the information from the Hall sensor to control conductivity of a switch. In at least one embodiment, controlling conductivity of the switch controls a drive current for a load. In at least one embodiment, utilizing the Hall sensor to detect the controlled current iCCT is more accurate than using a sense resistor (such as sense resistor 109 (
Although the present invention has been described in detail, it should be understood that various changes, substitutions and alterations can be made hereto without departing from the spirit and scope of the invention as defined by the appended claims. For example, in at least one embodiment, the controlled current sensed by the Hall sensor 203 is representative of an actual controlled current iCCT but is not the current flowing through the load. For example, in at least one embodiment, a current mirror can be used to mirror the controlled current iCCT and the controlled current sensed by the Hall sensor 203 is the mirrored current.
Number | Name | Date | Kind |
---|---|---|---|
3316495 | Sherer | Apr 1967 | A |
3423689 | Miller et al. | Jan 1969 | A |
3586988 | Weekes | Jun 1971 | A |
3725804 | Langan | Apr 1973 | A |
3790878 | Brokaw | Feb 1974 | A |
3881167 | Pelton et al. | Apr 1975 | A |
4075701 | Hofmann | Feb 1978 | A |
4334250 | Theus | Jun 1982 | A |
4409476 | Lofgren et al. | Oct 1983 | A |
4414493 | Henrich | Nov 1983 | A |
4476706 | Hadden et al. | Oct 1984 | A |
4523128 | Stamm | Jun 1985 | A |
4677366 | Wilkinson et al. | Jun 1987 | A |
4683529 | Bucher | Jul 1987 | A |
4700188 | James | Oct 1987 | A |
4737658 | Kronmuller et al. | Apr 1988 | A |
4797633 | Humphrey | Jan 1989 | A |
4937728 | Leonardi | Jun 1990 | A |
4940929 | Williams | Jul 1990 | A |
4973919 | Allfather | Nov 1990 | A |
4979087 | Sellwood et al. | Dec 1990 | A |
4980898 | Silvian | Dec 1990 | A |
4992919 | Lee et al. | Feb 1991 | A |
4994952 | Silva et al. | Feb 1991 | A |
5001620 | Smith | Mar 1991 | A |
5055746 | Hu et al. | Oct 1991 | A |
5109185 | Ball | Apr 1992 | A |
5121079 | Dargatz | Jun 1992 | A |
5206540 | de Sa e Silva et al. | Apr 1993 | A |
5264780 | Bruer et al. | Nov 1993 | A |
5278490 | Smedley | Jan 1994 | A |
5323157 | Ledzius et al. | Jun 1994 | A |
5359180 | Park et al. | Oct 1994 | A |
5383109 | Maksimovic et al. | Jan 1995 | A |
5424932 | Inou et al. | Jun 1995 | A |
5477481 | Kerth | Dec 1995 | A |
5479333 | McCambridge et al. | Dec 1995 | A |
5481178 | Wilcox et al. | Jan 1996 | A |
5565761 | Hwang | Oct 1996 | A |
5589759 | Borgato et al. | Dec 1996 | A |
5638265 | Gabor | Jun 1997 | A |
5691890 | Hyde | Nov 1997 | A |
5747977 | Hwang | May 1998 | A |
5757635 | Seong | May 1998 | A |
5764039 | Choi et al. | Jun 1998 | A |
5768111 | Zaitsu | Jun 1998 | A |
5781040 | Myers | Jul 1998 | A |
5783909 | Hochstein | Jul 1998 | A |
5798635 | Hwang et al. | Aug 1998 | A |
5900683 | Rinehart et al. | May 1999 | A |
5912812 | Moriarty, Jr. | Jun 1999 | A |
5929400 | Colby et al. | Jul 1999 | A |
5946202 | Balogh | Aug 1999 | A |
5946206 | Shimizu et al. | Aug 1999 | A |
5952849 | Haigh et al. | Sep 1999 | A |
5960207 | Brown | Sep 1999 | A |
5962989 | Baker | Oct 1999 | A |
5963086 | Hall | Oct 1999 | A |
5966297 | Minegishi | Oct 1999 | A |
5994885 | Wilcox et al. | Nov 1999 | A |
6016038 | Mueller et al. | Jan 2000 | A |
6037763 | Trontelj | Mar 2000 | A |
6043633 | Lev et al. | Mar 2000 | A |
6072969 | Yokomori et al. | Jun 2000 | A |
6083276 | Davidson et al. | Jul 2000 | A |
6084450 | Smith et al. | Jul 2000 | A |
6091233 | Hwang | Jul 2000 | A |
6125046 | Jang et al. | Sep 2000 | A |
6150774 | Mueller et al. | Nov 2000 | A |
6181114 | Hemena et al. | Jan 2001 | B1 |
6211626 | Lys et al. | Apr 2001 | B1 |
6211627 | Callahan | Apr 2001 | B1 |
6229271 | Liu | May 2001 | B1 |
6229292 | Redl et al. | May 2001 | B1 |
6246183 | Buonavita | Jun 2001 | B1 |
6259614 | Ribarich et al. | Jul 2001 | B1 |
6300723 | Wang et al. | Oct 2001 | B1 |
6304066 | Wilcox et al. | Oct 2001 | B1 |
6304473 | Telefus et al. | Oct 2001 | B1 |
6343026 | Perry | Jan 2002 | B1 |
6344811 | Melanson | Feb 2002 | B1 |
6369525 | Chang et al. | Apr 2002 | B1 |
6385063 | Sadek et al. | May 2002 | B1 |
6392400 | Lancaster et al. | May 2002 | B1 |
6407514 | Glaser et al. | Jun 2002 | B1 |
6407515 | Hesler | Jun 2002 | B1 |
6407691 | Yu | Jun 2002 | B1 |
6441558 | Muthu et al. | Aug 2002 | B1 |
6445600 | Ben-Yaakov | Sep 2002 | B2 |
6452521 | Wang | Sep 2002 | B1 |
6469484 | L'Hermite et al. | Oct 2002 | B2 |
6495964 | Muthu et al. | Dec 2002 | B1 |
6509913 | Martin, Jr. et al. | Jan 2003 | B2 |
6531854 | Hwang | Mar 2003 | B2 |
6580258 | Wilcox et al. | Jun 2003 | B2 |
6583550 | Iwasa et al. | Jun 2003 | B2 |
6628106 | Batarseh et al. | Sep 2003 | B1 |
6636003 | Rahm et al. | Oct 2003 | B2 |
6646848 | Yoshida et al. | Nov 2003 | B2 |
6657417 | Hwang | Dec 2003 | B1 |
6688753 | Calon et al. | Feb 2004 | B2 |
6713974 | Patchornik et al. | Mar 2004 | B2 |
6724174 | Esteves et al. | Apr 2004 | B1 |
6727832 | Melanson | Apr 2004 | B1 |
6737845 | Hwang | May 2004 | B2 |
6741123 | Anderson et al. | May 2004 | B1 |
6753661 | Muthu et al. | Jun 2004 | B2 |
6756772 | McGinnis | Jun 2004 | B2 |
6768655 | Yang et al. | Jul 2004 | B1 |
6781351 | Mednik et al. | Aug 2004 | B2 |
6788011 | Mueller et al. | Sep 2004 | B2 |
6806659 | Mueller et al. | Oct 2004 | B1 |
6839247 | Yang | Jan 2005 | B1 |
6860628 | Robertson et al. | Mar 2005 | B2 |
6870325 | Bushell et al. | Mar 2005 | B2 |
6873065 | Haigh et al. | Mar 2005 | B2 |
6882552 | Telefus et al. | Apr 2005 | B2 |
6888322 | Dowling et al. | May 2005 | B2 |
6894471 | Corva et al. | May 2005 | B2 |
6933706 | Shih | Aug 2005 | B2 |
6940733 | Schie et al. | Sep 2005 | B2 |
6944034 | Shytenberg et al. | Sep 2005 | B1 |
6956750 | Eason et al. | Oct 2005 | B1 |
6958920 | Mednik et al. | Oct 2005 | B2 |
6963496 | Bimbaud | Nov 2005 | B2 |
6967448 | Morgan et al. | Nov 2005 | B2 |
6970503 | Kalb | Nov 2005 | B1 |
6975079 | Lys et al. | Dec 2005 | B2 |
6975523 | Kim et al. | Dec 2005 | B2 |
6980446 | Simada et al. | Dec 2005 | B2 |
7003023 | Krone et al. | Feb 2006 | B2 |
7034611 | Oswal et al. | Apr 2006 | B2 |
7050509 | Krone et al. | May 2006 | B2 |
7064498 | Dowling et al. | Jun 2006 | B2 |
7064531 | Zinn | Jun 2006 | B1 |
7072191 | Nakao et al. | Jul 2006 | B2 |
7075329 | Chen et al. | Jul 2006 | B2 |
7078963 | Andersen et al. | Jul 2006 | B1 |
7088059 | McKinney et al. | Aug 2006 | B2 |
7099163 | Ying | Aug 2006 | B1 |
7102902 | Brown et al. | Sep 2006 | B1 |
7106603 | Lin et al. | Sep 2006 | B1 |
7109791 | Epperson et al. | Sep 2006 | B1 |
7126288 | Ribarich et al. | Oct 2006 | B2 |
7135824 | Lys et al. | Nov 2006 | B2 |
7145295 | Lee et al. | Dec 2006 | B1 |
7158633 | Hein | Jan 2007 | B1 |
7161816 | Shytenberg et al. | Jan 2007 | B2 |
7180250 | Gannon | Feb 2007 | B1 |
7183957 | Melanson | Feb 2007 | B1 |
7221130 | Ribeiro et al. | May 2007 | B2 |
7233135 | Noma et al. | Jun 2007 | B2 |
7246919 | Porchia et al. | Jul 2007 | B2 |
7255457 | Ducharm et al. | Aug 2007 | B2 |
7265531 | Stauth et al. | Sep 2007 | B2 |
7266001 | Notohamiprodjo et al. | Sep 2007 | B1 |
7276861 | Shteynberg et al. | Oct 2007 | B1 |
7288902 | Melanson | Oct 2007 | B1 |
7292013 | Chen et al. | Nov 2007 | B1 |
7310244 | Yang et al. | Dec 2007 | B2 |
7345458 | Kanai et al. | Mar 2008 | B2 |
7375476 | Walter et al. | May 2008 | B2 |
7388764 | Huynh et al. | Jun 2008 | B2 |
7394210 | Ashdown | Jul 2008 | B2 |
7414389 | Nguyen | Aug 2008 | B2 |
7511437 | Lys et al. | Mar 2009 | B2 |
7538499 | Ashdown | May 2009 | B2 |
7545130 | Latham | Jun 2009 | B2 |
7554473 | Melanson | Jun 2009 | B2 |
7569996 | Holmes et al. | Aug 2009 | B2 |
7583136 | Pelly | Sep 2009 | B2 |
7656103 | Shteynberg et al. | Feb 2010 | B2 |
7667986 | Artusi et al. | Feb 2010 | B2 |
7710047 | Shteynberg et al. | May 2010 | B2 |
7719246 | Melanson | May 2010 | B2 |
7719248 | Melanson | May 2010 | B1 |
7746043 | Melanson | Jun 2010 | B2 |
7746671 | Radecker et al. | Jun 2010 | B2 |
7750615 | Jung et al. | Jul 2010 | B2 |
7750738 | Bach | Jul 2010 | B2 |
7756896 | Feingold | Jul 2010 | B1 |
7777563 | Midya et al. | Aug 2010 | B2 |
7804256 | Melanson | Sep 2010 | B2 |
7804480 | Jeon et al. | Sep 2010 | B2 |
7923973 | Odell | Apr 2011 | B2 |
8040114 | Saint-Pierre | Oct 2011 | B2 |
20020065583 | Okada | May 2002 | A1 |
20020145041 | Muthu et al. | Oct 2002 | A1 |
20020150151 | Krone et al. | Oct 2002 | A1 |
20020166073 | Nguyen et al. | Nov 2002 | A1 |
20020186010 | Kliemannel | Dec 2002 | A1 |
20030095013 | Melanson et al. | May 2003 | A1 |
20030174520 | Bimbaud | Sep 2003 | A1 |
20030223255 | Ben-Yaakov | Dec 2003 | A1 |
20040004465 | McGinnis | Jan 2004 | A1 |
20040046683 | Mitamura et al. | Mar 2004 | A1 |
20040085030 | Laflamme et al. | May 2004 | A1 |
20040085117 | Melbert et al. | May 2004 | A1 |
20040169477 | Yancie et al. | Sep 2004 | A1 |
20040227571 | Kuribayashi | Nov 2004 | A1 |
20040228116 | Miller et al. | Nov 2004 | A1 |
20040232971 | Kawasaki et al. | Nov 2004 | A1 |
20040239262 | Ido et al. | Dec 2004 | A1 |
20050057237 | Clavel | Mar 2005 | A1 |
20050156770 | Melanson | Jul 2005 | A1 |
20050168492 | Hekstra et al. | Aug 2005 | A1 |
20050184895 | Petersen et al. | Aug 2005 | A1 |
20050197952 | Shea et al. | Sep 2005 | A1 |
20050207190 | Gritter | Sep 2005 | A1 |
20050218838 | Lys | Oct 2005 | A1 |
20050222881 | Booker | Oct 2005 | A1 |
20050253533 | Lys et al. | Nov 2005 | A1 |
20050270813 | Zhang et al. | Dec 2005 | A1 |
20050275354 | Hausman, Jr. et al. | Dec 2005 | A1 |
20050275386 | Jepsen et al. | Dec 2005 | A1 |
20060002110 | Dowling | Jan 2006 | A1 |
20060022916 | Aiello | Feb 2006 | A1 |
20060023002 | Hara et al. | Feb 2006 | A1 |
20060116898 | Peterson | Jun 2006 | A1 |
20060125420 | Boone et al. | Jun 2006 | A1 |
20060184414 | Pappas et al. | Aug 2006 | A1 |
20060214603 | Oh et al. | Sep 2006 | A1 |
20060226795 | Walter et al. | Oct 2006 | A1 |
20060238136 | Johnson, III et al. | Oct 2006 | A1 |
20060261754 | Lee | Nov 2006 | A1 |
20060285365 | Huynh et al. | Dec 2006 | A1 |
20070024213 | Shteynberg et al. | Feb 2007 | A1 |
20070029946 | Yu et al. | Feb 2007 | A1 |
20070040512 | Jungwirth et al. | Feb 2007 | A1 |
20070053182 | Robertson | Mar 2007 | A1 |
20070055564 | Fourman | Mar 2007 | A1 |
20070096717 | Ishihara | May 2007 | A1 |
20070103949 | Tsuruya | May 2007 | A1 |
20070124615 | Orr | May 2007 | A1 |
20070126656 | Huang et al. | Jun 2007 | A1 |
20070182699 | Ha et al. | Aug 2007 | A1 |
20070285031 | Shteynberg et al. | Dec 2007 | A1 |
20080012502 | Lys | Jan 2008 | A1 |
20080027841 | Eder | Jan 2008 | A1 |
20080043504 | Ye et al. | Feb 2008 | A1 |
20080054815 | Kotikalapoodi et al. | Mar 2008 | A1 |
20080094055 | Monreal et al. | Apr 2008 | A1 |
20080116818 | Shteynberg et al. | May 2008 | A1 |
20080130322 | Artusi et al. | Jun 2008 | A1 |
20080130336 | Taguchi | Jun 2008 | A1 |
20080150433 | Tsuchida et al. | Jun 2008 | A1 |
20080154679 | Wade | Jun 2008 | A1 |
20080174291 | Hansson et al. | Jul 2008 | A1 |
20080174372 | Tucker et al. | Jul 2008 | A1 |
20080175029 | Jung et al. | Jul 2008 | A1 |
20080192509 | Dhuyvetter et al. | Aug 2008 | A1 |
20080224635 | Hayes | Sep 2008 | A1 |
20080232141 | Artusi et al. | Sep 2008 | A1 |
20080239764 | Jacques et al. | Oct 2008 | A1 |
20080259655 | Wei et al. | Oct 2008 | A1 |
20080278132 | Kesterson et al. | Nov 2008 | A1 |
20080278891 | Bidenbach et al. | Nov 2008 | A1 |
20090067204 | Ye et al. | Mar 2009 | A1 |
20090070188 | Scott et al. | Mar 2009 | A1 |
20090147544 | Melanson | Jun 2009 | A1 |
20090174479 | Yan et al. | Jul 2009 | A1 |
20090218960 | Lyons et al. | Sep 2009 | A1 |
20100072956 | Fiebrich et al. | Mar 2010 | A1 |
20100141317 | Szajnowski | Jun 2010 | A1 |
Number | Date | Country |
---|---|---|
19713814 | Oct 1998 | DE |
0585789 | Mar 1994 | EP |
0632679 | Jan 1995 | EP |
0838791 | Apr 1998 | EP |
0910168 | Apr 1999 | EP |
1014563 | Jun 2000 | EP |
1164819 | Dec 2001 | EP |
1213823 | Jun 2002 | EP |
1460775 | Sep 2004 | EP |
1528785 | May 2005 | EP |
2204905 AL | Jul 2010 | EP |
2069269 | Aug 1981 | GB |
WO 2006022107 | Mar 2006 | JP |
WO9725836 | Jul 1997 | WO |
0115316 | Jan 2001 | WO |
0197384 | Dec 2001 | WO |
0215386 | Feb 2002 | WO |
WO0227944 | Apr 2002 | WO |
02091805 | Nov 2002 | WO |
WO2006013557 | Feb 2006 | WO |
2006067521 | Jun 2006 | WO |
WO2006135584 | Dec 2006 | WO |
2007026170 | Mar 2007 | WO |
2007079362 | Jul 2007 | WO |
WO2008072160 | Jun 2008 | WO |
WO20080152838 | Dec 2008 | WO |
Entry |
---|
D. Hausman, Lutron, RTISS-TE Operation, Real-Time Illumination Stability Systems for Trailing-Edge (Reverse Phase Control) Dimmers, v. 1.0 Dec. 2004. |
International Rectifier, Data Sheet No. PD60230 revC, IR1150(S)(PbF), uPFC One Cycle Control PFC IC Feb. 5, 2007. |
Texas Instruments, Application Report SLUA308, UCC3817 Current Sense Transformer Evaluation, Feb. 2004. |
Texas Instruments, Application Report SPRA902A, Average Current Mode Controlled Power Factor Correctiom Converter using TMS320LF2407A, Jul. 2005. |
Unitrode, Design Note DN-39E, Optimizing Performance in UC3854 Power Factor Correction Applications, Nov. 1994. |
Fairchild Semiconductor, Application Note 42030, Theory and Application of the ML4821 Average Currrent Mode PFC Controller, Aug. 1997. |
Fairchild Semiconductor, Application Note AN4121, Design of Power Factor Correction Circuit Using FAN7527B, Rev.1.0.1, May 30, 2002. |
Fairchild Semiconductor, Application Note 6004, 500W Power-Factor-Corrected (PFC) Converter Design with FAN4810, Rev. 1.0.1, Oct. 31, 2003. |
Fairchild Semiconductor, FAN4822, ZVA Average Current PFC Controller, Rev. 1.0.1 Aug. 10, 2001. |
Fairchild Semiconductor, ML4821, Power Factor Controller, Rev. 1.0.2, Jun. 19, 2001. |
Fairchild Semiconductor, ML4812, Power Factor Controller, Rev. 1.0.4, May 31, 2001. |
Linear Technology, 100 Watt LED Driver, Linear Technology, 2006. |
Fairchild Semiconductor, FAN7544, Simple Ballast Controller, Rev. 1.0.0, 2004. |
Fairchild Semiconductor, FAN7532, Ballast Controller, Rev. 1.0.2, Jun. 2006. |
Fairchild Semiconductor, FAN7711, Ballast Control IC, Rev. 1.0.2, Mar. 2007. |
Fairchild Semiconductor, KA7541, Simple Ballast Controller, Rev. 1.0.3, 2001. |
ST Microelectronics, L6574, CFL/TL Ballast Driver Preheat and Dimming, Sep. 2003. |
ST Microelectronics, AN993, Application Note, Electronic Ballast with PFC Using L6574 and L6561, May 2004. |
International Search Report and Written Opinion for PCT/US2008/062384 dated Jan. 14, 2008. |
S. Dunlap et al., Design of Delta-Sigma Modulated Switching Power Supply, Circuits & Systems, Proceedings of the 1998 IEEE International Symposium, 1998. |
Freescale Semiconductor, Inc., Dimmable Light Ballast with Power Factor Correction, Design Reference Manual, DRM067, Rev. 1, Dec. 2005. |
J. Zhou et al., Novel Sampling Algorithm for DSP Controlled 2 kW PFC Converter, IEEE Transactions on Power Electronics, vol. 16, No. 2, Mar. 2001. |
A. Prodic, Compensator Design and Stability Assessment for Fast Voltage Loops of Power Factor Correction Rectifiers, IEEE Transactions on Power Electronics, vol. 22, No. 5, Sep. 2007. |
M. Brkovic et al., “Automatic Current Shaper with Fast Output Regulation and Soft-Switching,” S.15.0 Power Converters, Telecommunications Energy Conference, 1993. |
Dallas Semiconductor, Maxim, “Charge-Pump and Step-Up DC-DC Converter Solutions for Powering White LEDs in Series or Parallel Connections,” Apr. 23, 2002. |
Freescale Semiconductor, AN3052, Implementing PFC Average Current Mode Control Using the MC9S12E128, Nov. 2005. |
D. Maksimovic et al., “Switching Converters with Wide DC Conversion Range,” Institute of Electrical and Electronic Engineer's (IEEE) Transactions on Power Electronics, Jan. 1991. |
V. Nguyen et al., “Tracking Control of Buck Converter Using Sliding-Mode with Adaptive Hysteresis,” Power Electronics Specialists Conference, 1995. PESC apos; 95 Record., 26th Annual IEEE vol. 2, Issue , Jun. 18-22, 1995 pp. 1086-1093. |
S. Zhou et al., “A High Efficiency, Soft Switching DC-DC Converter with Adaptive Current-Ripple Control for Portable Applications,” IEEE Transactions on Circuits and Systems—II: Express Briefs, vol. 53, No. 4, Apr. 2006. |
K. Leung et al., “Use of State Trajectory Prediction in Hysteresis Control for Achieving Fast Transient Response of the Buck Converter,” Circuits and Systems, 2003. ISCAS apos;03. Proceedings of the 2003 International Symposium, vol. 3, Issue , May 25-28, 2003 pp. III-439-III-442 vol. 3. |
K. Leung et al., “Dynamic Hysteresis Band Control of the Buck Converter with Fast Transient Response,” IEEE Transactions on Circuits and Systems—II: Express Briefs, vol. 52, No. 7, Jul. 2005. |
Y. Ohno, Spectral Design Considerations for White LED Color Rendering, Final Manuscript, Optical Engineering, vol. 44, 111302 (2005). |
S. Skogstad et al., A Proposed Stability Characterization and Verification Method for High-Order Single-Bit Delta-Sigma Modulators, Norchip Conference, Nov. 2006 http://folk.uio.no/savskogs/pub/A—Proposed—Stability—Characterization.pdf. |
J. Turchi, Four Key Steps to Design a Continuous Conduction Mode PFC Stage Using the NCP1653, ON Semiconductor, Publication Order No. AND184/D, Nov. 2004. |
Megaman, D or S Dimming ESL, Product News, Mar. 15, 2007. |
J. Qian et al., New Charge Pump Power-Factor-Correction Electronic Ballast with a Wide Range of Line Input Voltage, IEEE Transactions on Power Electronics, vol. 14, No. 1, Jan. 1999. |
P. Green, A Ballast that can be Dimmed from a Domestic (Phase-Cut) Dimmer, IRPLCFL3 rev. b, International Rectifier, http://www.irf.com/technical-info/refdesigns/cfl-3.pdf, printed Mar. 24, 2007. |
J. Qian et al., Charge Pump Power-Factor-Correction Technologies Part II: Ballast Applications, IEEE Transactions on Power Electronics, vol. 15, No. 1, Jan. 2000. |
Chromacity Shifts in High-Power White LED Systems due to Different Dimming Methods, Solid-State Lighting, http://www.lrc.rpi.edu/programs/solidstate/completedProjects.asp?ID=76, printed May 3, 2007. |
S. Chan et al., Design and Implementation of Dimmable Electronic Ballast Based on Integrated Inductor, IEEE Transactions on Power Electronics, vol. 22, No. 1, Jan. 2007. |
M. Madigan et al., Integrated High-Quality Rectifier-Regulators, IEEE Transactions on Industrial Electronics, vol. 46, No. 4, Aug. 1999. |
T. Wu et al., Single-Stage Electronic Ballast with Dimming Feature and Unity Power Factor, IEEE Transactions on Power Electronics, vol. 13, No. 3, May 1998. |
F. Tao et al., “Single-Stage Power-Factor-Correction Electronic Ballast with a Wide Continuous Dimming Control for Fluorescent Lamps,” IEEE Power Electronics Specialists Conference, vol. 2, 2001. |
Azoteq, IQS17 Family, IQ Switch®—ProxSense™ Series, Touch Sensor, Load Control and User Interface, IQS17 Datasheet V2.00.doc, Jan. 2007. |
C. Dilouie, Introducing the LED Driver, EC&M, Sep. 2004. |
S. Lee et al., TRIAC Dimmable Ballast with Power Equalization, IEEE Transactions on Power Electronics, vol. 20, No. 6, Nov. 2005. |
L. Gonthier et al., EN55015 Compliant 500W Dimmer with Low-Losses Symmetrical Switches, 2005 European Conference on Power Electronics and Applications, Sep. 2005. |
Why Different Dimming Ranges? The Difference Between Measured and Perceived Light, 2000 http://www.lutron.com/ballast/pdf/LutronBallastpg3.pdf. |
D. Hausman, Real-Time Illumination Stability Systems for Trailing-Edge (Reverse Phase Control) Dimmers, Technical White Paper, Lutron, version 1.0, Dec. 2004, http://www.lutron.com/technical—info/pdf/RTISS-TE.pdf. |
Light Dimmer Circuits, www.epanorama.net/documents/lights/lightdimmer.html, printed Mar. 26, 2007. |
Light Emitting Diode, http://en.wikipedia.org/wiki/Light-emitting—diode, printed Mar. 27, 2007. |
Color Temperature, www.sizes.com/units/color—temperature.htm, printed Mar. 27, 2007. |
S. Lee et al., A Novel Electrode Power Profiler for Dimmable Ballasts Using DC Link Voltage and Switching Frequency Controls, IEEE Transactions on Power Electronics, vol. 19, No. 3, May 2004. |
Y. Ji et al., Compatibility Testing of Fluorescent Lamp and Ballast Systems, IEEE Transactions on Industry Applications, vol. 35, No. 6, Nov./Dec. 1999. |
National Lighting Product Information Program, Specifier Reports, “Dimming Electronic Ballasts,” vol. 7, No. 3, Oct. 1999. |
Supertex Inc., Buck-based LED Drivers Using the HV9910B, Application Note AN-H48, Dec. 28, 2007. |
D. Rand et al., Issues, Models and Solutions for Triac Modulated Phase Dimming of LED Lamps, Power Electronics Specialists Conference, 2007. |
Supertex Inc., HV9931 Unity Power Factor LED Lamp Driver, Application Note AN-H52, Mar. 7, 2007. |
Supertex Inc., 56W Off-line LED Driver, 120VAC with PFC, 160V, 350mA Load, Dimmer Switch Compatible, DN-H05, Feb. 2007. |
ST Microelectronics, Power Factor Corrector L6561, Jun. 2004. |
Fairchild Semiconductor, Application Note 42047 Power Factor Correction (PFC) Basics, Rev. 0.9.0 Aug. 19, 2004. |
M. Radecker et al., Application of Single-Transistor Smart-Power IC for Fluorescent Lamp Ballast, Thirty-Fourth Annual Industry Applications Conference IEEE, vol. 1, Oct. 3, 1999-Oct. 7, 1999. |
M. Rico-Secades et al., Low Cost Electronic Ballast for a 36-W Fluorescent Lamp Based on a Current-Mode-Controlled Boost Inverter for a 120-V DC Bus Power Distribution, IEEE Transactions on Power Electronics, vol. 21, No. 4, Jul. 2006. |
Fairchild Semiconductor, FAN4800, Low Start-up Current PFC/PWM Controller Combos, Nov. 2006. |
Fairchild Semiconductor, FAN4810, Power Factor Correction Controller, Sep. 24, 2003. |
Fairchild Semiconductor, FAN4822, ZVS Average Current PFC Controller, Aug. 10, 2001. |
Fairchild Semiconductor, FAN7527B, Power Factor Correction Controller, 2003. |
Fairchild Semiconductor, ML4821, Power Factor Controller, Jun. 19, 2001. |
Freescale Semiconductor, AN1965, Design of Indirect Power Factor Correction Using 56F800/E, Jul. 2005. |
International Search Report for PCT/US2008/051072, mailed Jun. 4, 2008. |
“HV9931 Unity Power Factor LED Lamp Driver, Initial Release”, Supertex Inc., Sunnyvale, CA USA 2005. |
AN-H52 Application Note: “HV9931 Unity Power Factor LED Lamp Driver” Mar. 7, 2007, Supertex Inc., Sunnyvale, CA, USA. |
Dustin Rand et al: “Issues, Models and Solutions for Triac Modulated Phase Dimming of LED Lamps” Power Electronics Specialists Conferrence, 2007. PESC 2007. IEEE, IEEE, P1, Jun. 1, 2007, pp. 1398-1404. |
Spiazzi G et al: “Analysis of a High-Power Factor Electronic Ballast for High Brightness Light Emitting Diodes” Power Electronics Specialists, 2005 IEEE 36th Conference on Jun. 12, 2005, Piscatawa, NJ, USA, IEEE, Jun. 12, 2005, pp. 1494-1499. |
International Search Report PCT/US2008/062381 dated Feb. 5, 2008. |
International Search Report PCT/US2008/056739 dated Dec. 3, 2008. |
Written Opinion of the International Searching Authority PCT/US2008/062381 dated Feb. 5, 2008. |
Ben-Yaakov et al, “The Dynamics of a PWM Boost Converter with Resistive Input” IEEE Transactions on Industrial Electronics, IEEE Service Center, Piscataway, NJ, USA, vol. 46, No. 3, Jun. 1, 1999. |
International Search Report PCT/US2008/062398 dated Feb. 5, 2008. |
Partial International Search Report PCT/US2008/062387 dated Feb. 5, 2008. |
Noon, Jim “UC3855A/B High Performance Power Factor Preregulator”, Texas Instruments, SLUA146A, May 1996, Revised Apr. 2004. |
International Search Report PCT/GB2006/003259 dated Jan. 12, 2007. |
Written Opinion of the International Searching Authority PCT/US2008/056739 dated Dec. 3, 2008. |
International Search Report PCT/US2008/056606 dated Dec. 3, 2008. |
Written Opinion of the International Searching Authority PCT/US2008/056606 dated Dec. 3, 2008. |
International Search Report PCT/US2008/056608 dated Dec. 3, 2008. |
Written Opinion of the International Searching Authority PCT/US2008/056608 dated Dec. 3, 2008. |
International Search Report PCT/GB2005/050228 dated Mar. 14, 2006. |
International Search Report PCT/US2008/062387 dated Jan. 10, 2008. |
Data Sheet LT3496 Triple Output LED Driver, Linear Technology Corporation, Milpitas, CA 2007. |
Linear Technology, News Release,Triple Output LED, LT3496, Linear Technology, Milpitas, CA, May 24, 2007. |
Mamano, Bob, “Current Sensing Solutions for Power Supply Designers”, Unitrode Seminar Notes SEM1200, 1999. |
http://toolbarpdf.com/docs/functions-and-features-of-inverters.html printed on Jan. 20, 2011. |
Linear Technology, “Single Switch PWM Controller with Auxiliary Boost Converter,” LT1950 Datasheet, Linear Technology, Inc. Milpitas, CA, 2003. |
Yu, Zhenyu, 3.3V DSP for Digital Motor Control, Texas Instruments, Application Report SPRA550 dated Jun. 1999. |
International Rectifier, Data Sheet No. PD60143-O, Current Sensing Single Channel Driver, El Segundo, CA, dated Sep. 8, 2004. |
Balogh, Laszlo, “Design and Application Guide for High Speed MOSFET Gate Drive Circuits” [Online] 2001, Texas Instruments, Inc., SEM-1400, Unitrode Power Supply Design Seminar, Topic II, TI literature No. SLUP133, XP002552367, Retrieved from the Internet: URL:htt/://focus.ti.com/lit/ml/slup169/slup169.pdf the whole document. |
ST Datasheet L6562, Transition-Mode PFC Controller, 2005, STMicroelectronics, Geneva, Switzerland. |
Maksimovic, Regan Zane and Robert Erickson, Impact of Digital Control in Power Electronics, Proceedings of 2004 International Symposium on Power Semiconductor Devices & Ics, Kitakyushu Apr. 5, 2010, Colorado Power Electronics Center, ECE Department, University of Colorado, Boulder, CO. |
Texas Instruments, 8-Pin Continuous Conduction Mode (CCM) PFC Controller, UCC28019A, SLUS828B, Dec. 2008, Revised Apr. 2009. |
Allegro, A1442 Low Voltage Full Bridge Brushless DC Motor Driver with Hall Commutation and Soft-Switching, and Reverse Battery, Short Circuit, and Thermal Shutdown Protection, printed Mar. 27, 2009. |
Texas Instruments, Interleaving Continuous Conduction Mode PFC Controller, UCC28070, SLUS794C, Nov. 2007, revised Jun. 2009, Texas Instruments, Dallas TX. |
Infineon, CCM-PFC Standalone Power Factor Correction (PFC) Controller in Continuous Conduction Mode (CCM), Version 2.1, Feb. 6, 2007. |
International Rectifier, IRAC1150-300W Demo Board, User's Guide, Rev 3.0, Aug. 2, 2005. |
International Rectifier, Application Note AN-1077,PFC Converter Design with IR1150 One Cycle Control IC, rev. 2.3, Jun. 2005. |
International Rectifier, Data Sheet PD60230 revC, Feb. 5, 2007. |
Lu et al, International Rectifier, Bridgeless PFC Implementation Using One Cycle Control Technique, 2005. |
Linear Technology, LT1248, Power Factor Controller, Apr. 20, 2007. |
ON Semiconductor, AND8123/D, Power Factor Correction Stages Operating in Critical Conduction Mode, Sep. 2003. |
ON Semiconductor, MC33260, GreenLine Compact Power Factor Controller: Innovative Circuit for Cost Effective Solutions, Sep. 2005. |
ON Semiconductor, NCP1605, Enhanced, High Voltage and Efficient Standby Mode, Power Factor Controller, Feb. 2007. |
ON Semconductor, NCP1606, Cost Effective Power Factor Controller, Mar. 2007. |
ON Semiconductor, NCP1654, Product Review, Power Factor Controller for Compact and Robust, Continuous Conduction Mode Pre-Converters, Mar. 2007. |
Philips, Application Note, 90W Resonant SMPS with TEA1610 SwingChip, AN99011, 1999. |
NXP, TEA1750, GreenChip III SMPS control IC Product Data Sheet, Apr. 6, 2007. |
Renesas, HA16174P/FP, Power Factor Correction Controller IC, Jan. 6, 2006. |
Renesas Technology Releases Industry's First Critical-Conduction-Mode Power Factor Correction Control IC Implementing Interleaved Operation, Dec. 18, 2006. |
Renesas, Application Note R2A20111 EVB, PFC Control IC R2A20111 Evaluation Board, Feb. 2007. |
STMicroelectronics, L6563, Advanced Transition-Mode PFC Controller, Mar. 2007. |
Texas Instruments, Application Note SLUA321, Startup Current Transient of the Leading Edge Triggered PFC Controllers, Jul. 2004. |
Texas Instruments, Application Report, SLUA309A, Avoiding Audible Noise at Light Loads when using Leading Edge Triggered PFC Converters, Sep. 2004. |
Texas Instruments, Application Report SLUA369B, 350-W, Two-Phase Interleaved PFC Pre-Regulator Design Review, Mar. 2007. |
Unitrode, High Power-Factor Preregulator, Oct. 1994. |
Texas Instruments, Transition Mode PFC Controller, SLUS515D, Jul. 2005. |
Unitrode Products From Texas Instruments, Programmable Output Power Factor Preregulator, Dec. 2004. |
Unitrode Products From Texas Instruments, High Performance Power Factor Preregulator, Oct. 2005. |
Texas Instruments, UCC3817 BiCMOS Power Factor Preregulator Evaluation Board User's Guide, Nov. 2002. |
Unitrode, L. Balogh, Design Note UC3854A/B and UC3855A/B Provide Power Limiting with Sinusoidal Input Current for PFC Front Ends, SLUA196A, Nov. 2001. |
A. Silva De Morais et al., A High Power Factor Ballast Using a Single Switch with Both Power Stages Integrated, IEEE Transactions on Power Electronics, vol. 21, No. 2, Mar. 2006. |
M. Ponce et al., High-Efficient Integrated Electronic Ballast for Compact Fluorescent Lamps, IEEE Transactions on Power Electronics, vol. 21, No. 2, Mar. 2006. |
A. R. Seidel et al., A Practical Comparison Among High-Power-Factor Electronic Ballasts with Similar Ideas, IEEE Transactions on Industry Applications, vol. 41, No. 6, Nov.-Dec. 2005. |
F. T. Wakabayashi et al, An Improved Design Procedure for LCC Resonant Filter of Dimmable Electronic Ballasts for Fluorescent Lamps, Based on Lamp Model, IEEE Transactions on Power Electronics, vol. 20, No. 2, Sep. 2005. |
J. A. Vilela Jr. et al, An Electronic Ballast with High Power Factor and Low Voltage Stress, IEEE Transactions on Industry Applications, vol. 41, No. 4, Jul./Aug. 2005. |
S. T.S. Lee et al., Use of Saturable Inductor to Improve the Dimming Characteristics of Frequency-Controlled Dimmable Electronic Ballasts, IEEE Transactions on Power Electronics, vol. 19, No. 6, Nov. 2004. |
M. K. Kazimierczuk et al., Electronic Ballast for Fluorescent Lamps, IEEETransactions on Power Electronics, vol. 8, No. 4, Oct. 1993. |
S. Ben-Yaakov et al., Statics and Dynamics of Fluorescent Lamps Operating at High Frequency: Modeling and Simulation, IEEE Transactions on Industry Applications, vol. 38, No. 6, Nov.-Dec. 2002. |
H. L. Cheng et al., A Novel Single-Stage High-Power-Factor Electronic Ballast with Symmetrical Topology, IEEE Transactions on Power Electronics, vol. 50, No. 4, Aug. 2003. |
J.W.F. Dorleijn et al., Standardisation of the Static Resistances of Fluorescent Lamp Cathodes and New Data for Preheating, Industry Applications Conference, vol. 1, Oct. 13, 2002-Oct. 18, 2002. |
Q. Li et al., An Analysis of the ZVS Two-Inductor Boost Converter under Variable Frequency Operation, IEEE Transactions on Power Electronics, vol. 22, No. 1, Jan. 2007. |
H. Peng et al, Modeling of Quantization Effects in Digitally Controlled DC-DC Converters, IEEE Transactions on Power Electronics, vol. 22, No. 1, Jan. 2007. |
G. Yao et al., Soft Switching Circuit for Interleaved Boost Converters, IEEE Transactions on Power Electronics, vol. 22, No. 1, Jan. 2007. |
C. M. De Oliviera Stein et al., A ZCT Auxiliary Communication Circuit for Interleaved Boost Converters Operating in Critical Conduction Mode, IEEE Transactions on Power Electronics, vol. 17, No. 6, Nov. 2002. |
W. Zhang et al., A New Duty Cycle Control Strategy for Power Factor Correction and FPGA Implementation, IEEE Transactions on Power Electronics, vol. 21, No. 6, Nov. 2006. |
H. Wu et al., Single Phase Three-Level Power Factor Correction Circuit with Passive Lossless Snubber, IEEE Transactions on Power Electronics, vol. 17, No. 2, Mar. 2006. |
O. Garcia et al., High Efficiency PFC Converter to Meet EN61000-3-2 and A14, Proceedings of the 2002 IEEE International Symposium on Industrial Electronics, vol. 3, 2002. |
P. Lee et al., Steady-State Analysis of an Interleaved Boost Converter with Coupled Inductors, IEEE Transactions on Industrial Electronics, vol. 47, No. 4, Aug. 2000. |
D.K.W. Cheng et al., A New Improved Boost Converter with Ripple Free Input Current Using Coupled Inductors, Power Electronics and Variable Speed Drives, Sep. 21-23, 1998. |
B.A. Miwa et al., High Efficiency Power Factor Correction Using Interleaved Techniques, Applied Power Electronics Conference and Exposition, Seventh Annual Conference Proceedings, Feb. 23-27, 1992. |
Z. Lai et al., A Family of Power-Factor-Correction Controllers, Twelfth Annual Applied Power Electronics Conference and Exposition, vol. 1, Feb. 23, 1997-Feb. 27, 1997. |
L. Balogh et al., Power-Factor Correction with Interleaved Boost Converters in Continuous-Inductor-Current Mode, Eighth Annual Applied Power Electronics Conference and Exposition, 1993. APEC '93. Conference Proceedings, Mar. 7, 1993-Mar. 11, 1993. |
Fairchild Semiconductor, Application Note 42030, Theory and Application of the ML4821 Average Current Mode PFC Controller, Oct. 25, 2000. |
Unitrode Products From Texas Instruments, BiCMOS Power Factor Preregulator, Feb. 2006. |
Power Integrations, Inc., “TOP200-4/14 TOPSwitch Family Three-terminal Off-line PWM Switch”, XP-002524650, Jul. 1996, Sunnyvale, California. |
Texas Instruments, SLOS318F, “High-Speed, Low Noise, Fully-Differential I/O Amplifiers,” THS4130 and THS4131, US, Jan. 2006. |
International Search Report and Written Opinion, PCT US20080062387, dated Feb. 5, 2008. |
International Search Report and Written Opinion, PCT US200900032358, dated Jan. 29, 2009. |
Hirota, Atsushi et al, “Analysis of Single Switch Delta-Sigma Modulated Pulse Space Modulation PFC Converter Effectively Using Switching Power Device,” IEEE, US, 2002. |
Prodic, Aleksandar, “Digital Controller for High-Frequency Rectifiers with Power Factor Correction Suitable for On-Chip Implementation,” IEEE, US, 2007. |
International Search Report and Written Opinion, PCT US20080062378, dated Feb. 5, 2008. |
International Search Report and Written Opinion, PCT US20090032351, dated Jan. 29, 2009. |
Erickson, Robert W. et al, “Fundamentals of Power Electronics,” Second Edition, Chapter 6, Boulder, CO, 2001. |
Prodic, A. et al, “Dead Zone Digital Controller for Improved Dynamic Response of Power Factor Preregulators,” IEEE, 2003. |
International Search Report and Written Report PCT US20080062428 dated Feb. 5, 2008. |
Analog Devices, “120 kHz Bandwidth, Low Distortion, Isolation Amplifier”, AD215, Norwood, MA, 1996. |
Burr-Brown, ISO120 and ISO121, “Precision Los Cost Isolation Amplifier,” Tucson AZ, Mar. 1992. |
Burr-Brown, ISO130, “High IMR, Low Cost Isolation Amplifier,” SBOS220, US, Oct. 2001. |