Symmetrical, Direct Coupled Laser Drivers

Abstract

Symmetrical, direct coupled laser drivers for high frequency applications. The laser drivers are in integrated circuit form and use a minimum of relatively small (low valued) external components for driving a laser diode coupled to the laser driver through transmission lines. An optional amplifier may be used to fix the voltage at an internal node at data frequency spectrum to improve circuit performance. Feedback to a bias input may also be used to fix the voltage at the internal node. Programmability and a burst mode capability may be included.

Description

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to the field of laser drivers, and more particularly to laser drivers for high frequency applications.

2. Prior Art

Laser drivers are well known in the prior art. However, current operating requirements at increased frequencies, lower voltages and higher efficiencies exceed the performance of current designs. Representative prior art laser driver designs may be found in U.S. Pat. Nos. 7,181,100 and 7,457,336, US Published Application Nos. 2009/0268767 and 2009/0201052. Some products currently on the market are described in data sheets MAX3656 and MAX3946 (Maxim Integrated Products, Inc.), ONET4201LD (Texas Instruments) and ADN2526 (Analog Devices).

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1 is simplified circuit diagram of an embodiment of the present invention.

FIG. 2 is simplified circuit diagram of another embodiment of the present invention.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS

Referring to FIG. 1, a circuit diagram for a preferred embodiment of the present invention may be seen. The circuitry in the rectangular outline labeled “External” is the only external circuitry needed, with the other circuitry shown being within a single integrated circuit. The external circuitry includes the laser diode LD coupled to the integrated circuit terminals OUTA and OUTC through transmission lines TL1 and TL2. An inductor L1 is connected between integrated circuit terminals VCC and OUTA, and a bypass capacitor is connected between VCC and the circuit ground. An inductor L2 is connected between the OUTC and the VBIAS terminals, and capacitor C2 is connected between the VBIAS terminal and the circuit ground.

The outputs OUTA and OUTC coupled through the transmission lines to the anode and cathode of the laser diode LD, respectively, are connected to the collectors of transistors T3 and T2, respectively. Transistor T3, biased by the bias voltage vcb, is a cascode transistor for transistor T1 of the differential transistor pair T1 and T2, which have their emitters coupled together and to ground through resistor R3. The collector of transistor T3 is coupled to the anode connection of laser diode LD through output terminal OUTA and transmission line TL1, and to the VCC terminal of the integrated circuit through resistor R1 and external inductor L1. No cascode transistor is used for transistor T2 of the differential pair because of the lack of voltage headroom, the headroom for cascode transistor T3 effectively being provided by the voltage drop across laser diode LD itself. Note that the drive provided by transistors T1 and T2 is a symmetrical differential drive for the laser diode LD.

The inputs to the bases of the differential pair T1 and T2 are the differential data inputs mod−′ and mod+′, respectively, which are the outputs of amplifier A4. Amplifier A4 provides a plus and minus differential output having a fixed differential voltage, with voltages set by the programmable I mod level block and with a state responsive to the inputs mod+ and mod−. With this connection, the transistor that is on at any one time (T1 or T2) will conduct a current equal to its base voltage minus its Vbe, all divided by the R3. Thus transistors T1 and T2 act as current sources so that rather than being on and off, each act as a current source or is off, responsive to the digital data inputs mod+ and mod−. User programmability of circuits and control loops in general are well known in the art, as is the biasing of a transistor as a current source, and accordingly are not shown in detail herein. As an alternative, the resistor R3 might be a programmable current source, though there may not be enough voltage headroom for such an embodiment, depending on the voltage VCC of the power source.

A second differential transistor pair T5 and T6 have their emitters connected together and to the circuit ground through resistor R4. The collector of transistor T5 is connected to cascode transistor T4 having its base and collector connected in common with the base and collector of cascode transistor T3, respectively. Transistor T6 has its collector connected through capacitor C3 to the VCC terminal of the integrated circuit, and to resistor R2. The other end of resistor R2 is connected to the collector of transistor T2 and to the cathode of the laser diode LD through integrated circuit terminal OUTC and transmission line TL2. The bases of transistors T5 and T6 are coupled as burst enable inputs bias−′ and bias+′, respectively, from amplifier A1 which controls the base voltages of transistors T5 and T6 responsive to the signals bias+ and bias−, and at voltage levels set by the Programmable I bias level block. Thus transistors also act as separately user programmable current sources like those of transistors T1 and T2 for the digital data inputs mod+ and mod−. In FIG. 1, the connections between the integrated circuit and the terminals VCC, OUTA, OUTC and VBIAS are shown as inductors, as the inductance of these connections at the high frequencies at which the present invention operates is meaningful and should be taken into consideration.

In one embodiment, additional circuitry is added to the input circuitry, namely to override the data inputs mod− high and mod+ low when bias− is high and bias+ is low, independent of any actual data inputs the circuit may receive. This allows multiple laser drivers to share a communication channel in a time division multiplexing scheme where only one transmitter is enabled at any times. Of course the override is immediately released when bias+ goes high and bias− goes low (output burst enabled). As an example, such an override can be implemented various ways using simple logic functions.

The impedance of the typical laser diode is on the order of 5 to 10 ohms differentially, so there is a substantial impedance mismatch between the transmission lines (25 ohm transmission lines or 50 ohm differentially in one embodiment) coupled to the laser diode LD. However, resistors R1 and R2 are chosen to match the transmission lines, and provide the termination for the signal reflected back from the laser diode LD through the transmission lines, resistor R1 being directly connected to VCC and R2 being AC coupled to VCC through capacitor C3 at the frequencies of operation. Thus there is symmetry in the external circuitry as well as in the drive and termination of the 25 ohm transmission lines.

When the output burst is not enabled (and mod− is held high and mod+ is held low as previously described), there is no current through the laser diode LD as there is no DC connection to its cathode. Thus there is no light emission from the laser diode. The voltage at OUTA is essentially VCC, i.e., the voltage across inductor L1 is essentially zero because of its low resistance. When the output burst is enabled and mod+ is high for transmitting a “1”, current flows through the laser diode LD, with a primary current path through transistor T2 and resistor R3 to the circuit ground, transistor T2 acting as a current source controlled by the output voltage levels of amplifier A4, which in turn provides output voltage levels controlled by the programmable I mod level block).

When the output burst is enabled and Mod− is high for transmission of a “0”, transistor T2 will be off. Now the component of the current through the laser diode LD and transistor T2 is off, so that the only remaining component of current is that though resistor R2, transistor T6 and resistor R4. Note that in essence, transistors T2 and T1 steer the current component of the current sources of transistors T2 and T1 through the laser diode LD through and around the laser diode, respectively. This in turn means that the average current through external inductor L1 is constant, independent of whether a “1” or a “0” is being transmitted.

It may be seen from the foregoing that the structure of the laser driver just described and illustrated in FIG. 1 is a symmetrical, differential direct coupled laser driver structure with burst mode capabilities. Of particular interest is the fact that the data and bias loops are coupled together, the current for the transmission of a “1” being coupled through the bias loop.

Circuit performance may be optionally improved by actively fixing the voltage of the node VBIAS, at least with respect to high frequency signals (i.e., signals in the data frequency spectrum, as opposed to low frequencies which are frequencies well below the data frequency spectrum). For this purpose, the optional circuit in the box at the left of FIG. 1 can be added. This circuit is, in essence, an amplifier A(s) with a complex transfer function and with a feedback resistor R7 as shown in the oval outline in FIG. 1. It has an output impedance for the output VBIAS that is very low at the high frequencies, i.e., looks like a voltage source, but which is very high for low frequencies, i.e., looks like a current source. At high frequencies, it can be considered to make capacitor C3 look very large, thereby improving the termination of the cathode and thus the circuit balance. At low frequencies, the circuit will seek an output VBIAS equal to the average voltage on the node to which it is connected.

Now referring to the circuit to the left of FIG. 1 within the outline, transistor T7 is coupled through resistor R5 as an emitter follower biased by current source 11. The circuit to the left of transistor T7 is an amplifier responsive at high frequencies to changes in the voltage on the emitter of transistor T7, the voltage VBIAS, by feedback through resistor R7, to adjust the voltage on the base of transistor T7 to cancel or greatly reduce such changes.

In particular, a change in the voltage VBIAS changes the current through transistor T8, changing the voltage drop across resistor R6, coupling that change through the base emitter voltage of transistor T9 biased by current source 13 to the base of transistor T11. This changes the current through transistor T11 which causes the voltage drop through resistor R8 to change, feeding this change back to the base of transistor T7 to resist the change in VBIAS that initiated the disturbance.

The bases of transistors T7 and T8 are coupled to VCC through resistors R8 and R9, respectively, and to the collectors of differential transistor pair T11 and T10, respectively. The base of transistor T10 is connected to a reference voltage, with the common emitter connection of transistors T10 and T11 being biased by the current through transistor T12. The voltage on capacitor C6 connected to the gate of transistor T12 integrates the output of the voltage controlled current source 14 (transconductance Gm), which is proportional to the difference in voltages on the collectors of transistors T7 and T8. If at a low frequency (relative to the data frequencies), VBIAS changes, that will cause a current through resistor R5, which in turn will cause a change in voltage on capacitor C4. That causes a voltage difference across voltage controlled current source 14, unbalancing the voltage across the voltage controlled current source 14 to charge or discharge capacitor C6 until the circuit settles at the new value of VBIAS.

Capacitor C4 provides a capacitive load on the collector of transistor T7 at data frequencies to limit the fluctuations of the voltage on the collector of transistor T7 to avoid saturation of the transistor. Capacitor C5, on the other hand, determines the circuit response to frequencies in a mid-frequency range.

As an alternative to the circuit at the left of FIG. 1, the disturbances in VBIAS at data frequencies may be substantially eliminated using the circuit of FIG. 2. This circuit, like that of FIG. 1, senses any attempted change in VBIAS at data frequencies, but in addition to directly adjusting VBIAS, provides feedback to transistors T5 and T6 so that transistor T6 will also provide (or absorb) the current component that is attempting to vary VBIAS at the data frequencies. The end result is the same as that achieved by the circuit at the left of FIG. 1, though the feedback is both directly to VBIAS itself as in the circuit of FIG. 1, and indirectly to VBIAS through transistor T6.

Referring again to FIG. 2, resistors R4, R5 and R7, transistors T5, T6 and T7, current source 11 and signals bias+ and bias− are the same as in FIG. 1, the rest of the right side of FIG. 1 being omitted in FIG. 2 for clarity, though could be identical to that of FIG. 1. In operation, resistor R7 senses any change in the VBIAS voltage, which change is amplified by amplifier A′(s) and fed back to the base of transistor T7. Amplifier A′(s) can have a transfer function f(s) that produces the same VBIAS voltage characteristics (acts like a voltage source at data frequencies and as a current source at low frequencies) as the circuit in the box at the left of FIG. 1. Actually taking out amplifiers A2 and A3, the circuit shown in FIG. 2 may be considered a simplified representation of the corresponding part of the circuit of FIG. 1.

Amplifier A1 is shown in FIG. 1, though with only one programmable input for bias control. In FIG. 2, additional inputs are provided for control through amplifiers A2 and/or A3. Normally both path 2 and path 3 would not be used, and without path 2 and path 3, but only path 1, one has a simplified version of the respective part of the circuit of FIG. 1. Again, paths 1, 2 and 3 may be eliminated, though performance is improved and the size of the external components, especially inductor L2 and capacitor C2 may be reduced by using at least feedback path 1, as previously described. Also if path 2 is used (i.e., paths 1 and 2 are used), then capacitor C4 may be eliminated, or substantially reduced in capacitance.

The present invention has been disclosed and described with respect to npn transistors, though it should be noted that it can be implemented in other technologies, such as by way of example, using NMOS transistors. In any case, each transistor, regardless of type, may be characterized as having first, second and third terminals wherein the voltage between the first (emitter or source) and second terminals (base or gate) controls the conduction of current between the third (collector or drain) and first (emitter or source) terminals. Also transistors T3 and T4 are cascode transistors, and may be eliminated if desired, as long as transistors T1 and T5 can handle the higher voltage that they will be subjected to. In that regard, the topology of the invention may be inverted and implemented with transistors of the opposite conductivity type.

There have been disclosed herein symmetrical, differential direct coupled laser driver structures with burst mode capabilities that operate on low supply voltages with high efficiency. While certain preferred embodiments of the present invention have been disclosed and described herein for purposes of illustration and not for purposes of limitation, it will be understood by those skilled in the art that various changes in form and detail may be made therein without departing from the spirit and scope of the invention.

Claims

1. A laser diode driver comprising: a power supply connection, a laser diode anode connection, a laser diode cathode connection, a first bias connection and a circuit ground connection;a first resistor coupled between the power supply connection and the laser diode anode connection;a second resistor coupled between the laser diode cathode connection and the bias connection;a current source coupled between the first bias connection and the circuit ground connection;first and second transistors, each having first, second and third terminals wherein the voltage between the first and second terminals controls the conduction between the third and first terminals, the first and second transistors having their first terminals coupled together and to the circuit ground connection, the third terminal of the first transistor being coupled to the laser diode anode connection, the second terminals of the first and second transistors being coupled to a first differential voltage source responsive to differential data inputs to controllably turn on either of the first and second transistors as a current source of a first differential current source and to turn off the other of the first and second transistors as defined by the differential data inputs;the second transistor having its third terminal coupled to the laser diode cathode connection.

2. The laser diode driver of claim 1 further comprising a third transistor having first, second and third terminals wherein the voltage between the first and second terminals controls the conduction between the third and first terminals, the third transistor having its first terminal coupled to the third terminal of the first transistor, its second terminal coupled to a second bias connection and its third terminal coupled to the laser diode anode connection, whereby the third terminal of the first transistor is coupled to the laser diode anode connection through the third transistor.

3. The laser diode driver of claim 2 wherein the current source coupled between the bias connection and the circuit ground connection comprises: fourth, fifth and sixth transistors, each having first, second and third terminals wherein the voltage between the first and second terminals controls the conduction between the third and first terminals, the fourth transistor having its third terminal coupled to the laser diode anode connection, its second terminal coupled to the second bias connection and its first terminal coupled to the third terminal of the fifth transistor, the third terminal of the sixth transistor being coupled to the bias connection, the first terminals of the fifth and sixth transistors being coupled to the circuit ground connection, and the second terminals of the fifth and sixth transistors being coupled to a second differential voltage source responsive to differential burst enable inputs to controllably turn on either of the fifth and sixth transistors as the current source of the second differential current source and to turn off the other of the fifth and sixth transistors as defined by the differential burst enable inputs, the sixth transistor when on, acting as the current source coupled between the bias connection and the circuit ground connection.

4. The laser diode driver of claim 1 further comprising a capacitor coupled between the bias connection and the power supply connection.

5. The laser diode driver of claim 1 wherein the current source coupled between the bias connection and the circuit ground connection comprises: third and fourth transistors, each having first, second and third terminals wherein the voltage between the first and second terminals controls the conduction between the third and first terminals, the first terminals of the third and fourth transistors being coupled to the circuit ground connection, and the second terminals of the third and fourth transistors being coupled to a second differential voltage source responsive to differential burst enable inputs to controllably turn on either of the third and fourth transistors as the current source of the second differential current source and to turn off the other of the third and fourth transistors as defined by the differential burst enable inputs, the fourth transistor when on, acting as the current source coupled between the first bias connection and the circuit ground connection.

6. The laser diode driver of claim 5 wherein the first and second differential voltage sources are programmable.

7. The laser diode driver of claim 3 further comprised of an amplifier having an output coupled to the first bias connection, the amplifier having a complex transfer function providing a low output impedance at high frequencies and a high output impedance at low frequencies.

8. The laser diode driver of claim 7 further comprised of a seventh transistor having first, second and third terminals wherein the voltage between the first and second terminals controls the conduction between the third and first terminals, and wherein the seventh transistor is coupled as an first terminal follower output of the amplifier.

9. The laser diode driver of claim 8 wherein the second differential current source is coupled to be responsive to the voltage on the third terminal of the seventh transistor to resist voltage changes in the data frequency spectrum on the output of the amplifier.

10. The laser diode driver of claim 8 wherein the second differential current source is coupled to be responsive to the voltage on the first terminal of the seventh transistor to resist voltage changes in the data frequency spectrum on the output of the amplifier.

11. The laser diode driver of claim 8 further comprising: a first inductor coupled between the power supply connection and the laser diode anode connection;a first capacitor coupled between the power supply connection and the circuit ground connection;a second inductor coupled between the laser diode cathode connection and the bias connection; anda second capacitor coupled between the bias connection and the circuit ground connection.

12. A laser diode driver comprising: a power supply connection, a laser diode anode connection, a laser diode cathode connection, a bias connection and a circuit ground connection;a first resistor coupled between the power supply connection and the laser diode anode connection;a second resistor coupled between the laser diode cathode connection and the bias connection;a current source coupled between the bias connection and the circuit ground connection;first and second transistors, each having first, second and third terminals wherein the voltage between the first and second terminals controls the conduction between the third and first terminals, the first and second transistors having their second terminals coupled to be responsive to differential data inputs to controllably turn on either of the first and second transistors as a current source of a first differential current source and to turn off the other of the first and second transistors as defined by the differential data inputs;the first transistor having its third terminal to the anode connection and the second transistor having its third terminal coupled to the laser diode cathode connection.

13. The laser diode driver of claim 12 further comprising a third transistor having first, second and third terminals wherein the voltage between the first and second terminals controls the conduction between the third and first terminal, the third transistor having its first terminal coupled to the third terminal of the first transistor, its second terminal coupled to a bias voltage and its third terminal coupled to the laser diode anode connection, whereby the third connection of the first transistor is coupled to the anode connection through the third transistor.

14. The laser diode driver of claim 12 wherein the first differential current source is programmable.

15. The laser diode driver of claim 12 further comprising a capacitor coupled between the first bias connection and the power supply connection.

16. The laser diode driver of claim 12 wherein the current source coupled between the first bias connection and the circuit ground connection comprises: third and fourth transistors, each having first, second and third terminals wherein the voltage between the first and second terminals controls the conduction between the third and first terminals, the first terminals of the third and fourth transistors being coupled to the circuit ground connection, and the second terminals of the third and fourth transistors being coupled to differential burst enable inputs to controllably turn on either of the third and fourth transistors as the current source of the second differential current source and to turn off the other of the third and fourth transistors as defined by the differential burst enable inputs, the fourth transistor when on, acting as the current source coupled between the first bias connection and the circuit ground connection.

17. The laser diode driver of claim 16 wherein the second differential current source is programmable

18. The laser diode driver of claim 16 further comprised of an amplifier having an output coupled to the first bias connection, the amplifier having a complex transfer function providing a low output impedance at high frequencies and a high output impedance at low frequencies.

19. The laser diode driver of claim 18 further comprised of a fifth transistor having first, second and third terminals wherein the voltage between the first and second terminals controls the conduction between the third and first terminals, the fifth transistor coupled as a first terminal follower output of the amplifier.

20. The laser diode driver of claim 19 wherein the second differential current source is coupled to be responsive to the voltage on the third terminal of the fifth transistor to resist voltage changes at data spectrum frequencies on the output of the amplifier.

21. The laser diode driver of claim 19 wherein the second differential current source is coupled to be responsive to the voltage on the first terminal of the fifth transistor to resist voltage changes at data rates on the output of the amplifier.

22. The laser diode driver of claim 19 further comprising: a first inductor coupled between the power supply connection and the laser diode anode connection;a first capacitor coupled between the power supply connection and the circuit ground connection;a second inductor coupled between the laser diode cathode connection and the first bias connection; anda second capacitor coupled between the bias connection and the circuit ground connection.