Patent Grant
8564384
1. Field of the Invention
The present invention relates to a variable resonator, a tunable bandwidth filter, and an electric circuit device using the same.
2. Description of the Related Art
In the field of high frequency radio communication, necessary signals and unnecessary signals are separated by taking out a signal of particular frequency from a large number of signals. A circuit serving the function is called a filter, and is mounted on many radio communication devices.
In a general filter, center frequency, bandwidth or the like representing the characteristics of the filter are invariant. Even if you wish to adapt radio communication devices using such a filter to the application for various frequencies, it is impossible to operate the filter on frequency characteristics other than previously prepared frequency characteristics that each filter has.
Patent literature 1 given below discloses a filter to solve the problem which has resonators using piezoelectric bodies. A bias voltage is applied to the piezoelectric bodies from outside to change the frequency characteristics (resonance frequency) of the piezoelectric bodies and then the bandwidth of the filter is changed.
Although the tunable filter disclosed in the Patent literature 1 has a bandwidth as a ladder type filter, the changing width of the center frequency is as small as about 1% to 2% due to the limitation of the characteristics of the piezoelectric bodies. For this reason, variation of bandwidth is also about the same level, and a significant change of bandwidth is not possible.
Further, a method in which a plurality of filters having different combinations of center frequency and bandwidth are prepared and the filters are switched by a switch or the like corresponding to frequency application is easily considered. However, in this method, filters are necessary by the number of desired combinations of center frequency and bandwidth, and thus a circuit size increases. For this reason, the device increases in size.
On the other hand, miniaturization is not the best design. For example, if the filter is designed in order to obtain a desired performance, a circuit size becomes so small that actual manufacture is difficult in some cases.
In view of such circumstances, it is an object of the present invention to provide a variable resonator, a tunable filter and an electric circuit device, which can be manufactured in an arbitrary size while is capable of significantly changing bandwidth.
The variable resonator of the present invention comprises: a line body where one or a plurality of lines are constituted in a loop shape; a ground conductor; at least two switches; and at least three reactance circuits, wherein the switches have one ends electrically connected to different positions on the line body and the other ends electrically connected to the ground conductor, and are capable of switching electrical connection/non-connection between the ground conductor and the line body, the line section has a line length corresponding to one wavelength or integral multiple thereof at a resonance frequency which is determined corresponding to each reactance value of each reactance circuit, and the reactance circuit are electrically connected to the line body at predetermined intervals based on an electrical length at the resonance frequency. Hereinafter, the variable resonator is called a variable resonator X.
The variable resonator X may adopt the constitution that the line body is a single loop line and the reactance circuits are electrically connected to the loop line as branching circuits along the circumference direction of the loop line. Hereinafter, the variable resonator is called a variable resonator A.
The variable resonator A may adopt the constitution that the reactance circuits severally have the same reactance value and are connected to the loop line at the equal electrical length intervals.
The variable resonator A may adopt the constitution that the total number of the reactance circuits is M where M is an even number of 4 or larger; the reactance circuits severally have the same reactance value; M/2−1 reactance circuits are connected clockwise to a part of the loop line between a position K1 arbitrarily set on the loop line and a position K2 half the electrical length of one circumference of the loop line except the position K1 and the position K2 so as to divide the part at the equal electrical length intervals; M/2−1 reactance circuits are connected counter-clockwise to a remaining part of the loop line between the position K1 and the position K2 except the position K1 and the position K2 so as to divide the remaining part at the equal electrical length intervals, and two reactance circuits are connected to the position K2 of the loop line.
The variable resonator A may adopt the constitution that the total number of the reactance circuits is M−1 where M is an even number of 4 or larger; M−2 reactance circuits out of M−1 reactance circuits (hereinafter, referred to as first reactance circuits) severally have the same reactance value and remaining one reactance circuit (hereinafter, referred to as second reactance circuit) has half the value of the reactance value of each first reactance circuit; M/2−1 first reactance circuits are connected clockwise to a part of the loop line between a position K1 arbitrarily set on the loop line and a position K2 half the electrical length of one circumference of the loop line except the position K1 and the position K2 so as to divide the part at the equal electrical length intervals; M/2−1 first reactance circuits are connected counter-clockwise to a remaining part of the loop line between the position K1 and the position K2 except the position K1 and the position K2 so as to divide the remaining part at the equal electrical length intervals; and the second reactance circuit is connected to the position K2 of the loop line.
The variable resonator X may adopt the constitution that the line body is constituted of at least three lines; the switches have one ends electrically connected to any one of the lines at different positions and the other ends electrically connected to the ground conductor, and are capable of switching electrical connection/non-connection between the ground conductor and the line; the sum of the line lengths of the lines corresponds to one wavelength or integral multiple thereof at the resonance frequency in response to each reactance value of each reactance circuit; each line has a predetermined electrical length at the resonance frequency, and at least one reactance circuit is electrically connected in series between adjacent lines. Hereinafter, the variable resonator is called a variable resonator B.
The variable resonator B may adopt the constitution that the total number of the lines is N and the total number of the reactance circuits is N where N is an integer of 3 or larger, the reactance circuits severally have the same reactance value; each line has the same electrical length; and the reactance circuit is connected between adjacent lines.
The variable resonator B may adopt the constitution that the total number of the lines is M−1 and the total number of the reactance circuits is M where M is an even number of four or larger; the reactance circuits severally have the same reactance value; one reactance circuit is connected between an i-th line and an (i+1)-th line where i is an integer satisfying 1≦i<M/2; two reactance circuits in series connection are connected between an (M/2)-th line and an (M/2+1)-th line; one reactance circuit is connected between an i-th line and an (i+1)-th line where i is an integer satisfying M/2+1≦i<M−1; one reactance circuit is connected between an (M−1)-th line and the 1st line; an electrical length from a position K arbitrarily set on the 1st line to an end portion of the 1st line which is closer to the 2nd line and each electrical length of the i-th line where i is an integer satisfying 1≦i≦M/2 are equal, and an electrical length from the position K to the end portion of the first line which is closer to the (M−1)-th line and the electrical length of the i-th line where i is an integer satisfying M/2+1≦i≦M−1 are equal.
The variable resonator B may adopt the constitution that the total number of the lines is M−1 and the total number of the reactance circuits is M−1 where M is an even number of 4 or larger; M−2 reactance circuits out of M−1 reactance circuits (hereinafter, referred to as first reactance circuits) severally have the same reactance value and remaining one reactance circuit (hereinafter, referred to as a second reactance circuit) has a value twice the reactance value of each first reactance circuit; one first reactance circuit is connected between an i-th line and an (i+1)-th line where i is an integer satisfying 1≦i<M/2; the second reactance circuit is connected between an (M/2)-th line and an (M/2+1)-th line; one first reactance circuit is connected between an i-th line and an (i+1)-th line where i is an integer satisfying M/2+1≦i<M−1; one first reactance circuit is connected between an (M−1)-th line and the 1st line; an electrical length from a position K arbitrarily set on the 1st line to an end portion of the 1st line which is closer to the 2nd line and each electrical length of the i-th line where i is an integer satisfying 1≦i≦M/2 are equal; and an electrical length from the position K to an end portion of the 1st line which is closer to the (M−1)-th line and each electrical length of the i-th line where i an integer satisfying M/2+1≦i≦M−1 are equal.
In each constitution described above, a bandwidth straddling a resonance frequency can be changed significantly by changing a switch to be turned to a conduction state (ON state), and furthermore, the resonance frequency is not influenced with a change of switches to be selected. Further, since the size of the variable resonator can be decided by the reactance values of the reactance circuits, the variable resonator can be manufactured in an arbitrary size by constituting a reactance circuit having an appropriate reactance value.
In the above-described variable resonators (X, A, B), the line body is connected electrically to the ground conductor by any one of the switches.
The tunable bandwidth filter of the present invention comprises: at least one variable resonator X and a transmission line, wherein the variable resonator is connected electrically to the transmission line.
The passband width of a signal can be changed significantly by using the above-described variable resonator X, and furthermore, since the size of the variable resonator can be decided by the reactance value of each reactance circuit, the tunable bandwidth filter can be manufactured in an arbitrary size by constituting a reactance circuit having an appropriate reactance value.
The tunable bandwidth filter may adopt the constitution that at least two variable resonators are provided, wherein each of the variable resonators is connected to the transmission line as a branching circuit via a switch (hereinafter, referred to as a second switch) at the same coupled portion; and the transmission line is capable of being connected electrically to all or a part of the variable resonators by the selected second switch(es).
The electric circuit device of the present invention comprises: at least one variable resonator X and a transmission line T having a bent portion, wherein the bent portion of the transmission line T is connected electrically to the variable resonator.
The electric circuit device may adopt the constitution that a part of the variable resonator on an area where the bent portion of the transmission line T and the variable resonator are electrically connected and in the vicinity of the area is not parallel with the transmission line T.
According to the present invention, by a selecting of a switch to be turned to the ON state (electrically connected state) from a plurality of switches, it is possible to freely change the bandwidth while its resonance frequency (center frequency in the filter) sustains at a constant value. Further, since the size of the variable resonator can be decided by the reactance value of each reactance circuit, the variable resonator can be manufactured in an arbitrary size by constituting a reactance circuit having an appropriate reactance value. Note that the tunable bandwidth filter and the electric circuit device, which use the variable resonator of the present invention, can also enjoy the effect.
Further, in the variable resonator of the present invention, loss of signal at the resonance frequency is dominated by the parasitic resistances of the conductor line which mainly constitutes a variable resonator and the reactance circuits, influence of insertion loss by switches or the like is small. For this reason, the loss of a signal in the passband can be suppressed even if the tunable bandwidth filter is constituted of using switches or the like having large loss for the variable resonator.
Further, in the electric circuit device of the present invention, a bandwidth straddling the resonance frequency can be significantly changed, and additionally, an insertion loss caused by coupling with the variable resonator can be suppressed by using the variable resonator of the present invention.
[Circular Line Body]
As two specific modes of the variable resonator 900, a variable resonator 900a and a variable resonator 900b are exemplified respectively in
The variable resonator 900 is made up of a conductor line 902 (hereinafter, also simply called a “line” or a “loop line”) and two or more of switches 903. The line 902 is formed on one surface of a dielectric substrate 905 by a conductor such as metal. In the dielectric substrate 905, a ground conductor 904 is formed by a conductor such as metal and is formed on a surface (referred to as a rear surface) on the opposite side of the surface on which the line 902 is provided. In each switch 903, as shown in
The line 902 is a loop line which has a length of a phase change of 2π (360 degrees) at a desired resonance frequency, that is a length of one wavelength or integral multiple thereof at the resonance frequency. In the variable resonator 900 shown in
Herein, the “length” means the circumference of the loop line, and is a length from a certain position on the line to this position after making a full circle.
Herein, the “desired resonance frequency” is one element of performance generally required in a resonator, and is an arbitrary design matter. Although the variable resonator 900 may be used in an alternating-current circuit and a subject resonance frequency is not particularly limited, it is useful when the resonance frequency is set to a high frequency of 100 kHz or higher, for example.
In the present invention, it is desirable that the line 902 is a line having uniform characteristic impedance. Herein, “having uniform characteristic impedance” means that when the loop line 902 is cut with respect to a circumference direction so as to be fragmented into segments, these segments have severally the same characteristic impedance. Making the characteristic impedance precisely become completely the same value is not an essential technical matter, and manufacturing the line 902 so as to set the characteristic impedance to substantially the same value is enough from a practical viewpoint. Assuming that a direction orthogonal to the circumference direction of the line 902 is referred to as the width of the line 902, in the case where the relative permittivity of the dielectric substrate 905 is uniform, the line 902 formed to have substantially the same width at any point has a uniform characteristic impedance.
A difference between the variable resonator 900a and the variable resonator 900b is whether the other end 932 of the switch 903 is provided inside the line 902 or provided outside thereof. The other end 932 of the switch 903 is provided outside the line 902 in the variable resonator 900a, and the other end 932 of the switch 903 provided inside the line 902 in the variable resonator 900b.
Hereinafter, description will be made on the assumption that the loop line body 101 is the variable resonator 900. Further, to prevent drawings from becoming complicated, illustration of the switches 903 may be omitted in showing the circular line body 101.
[Reactance Circuits]
Assuming that an impedance Z is expressed in Z=R+jX (j is an imaginary unit), the reactance circuit 102 is a reactance circuit with R=0 regarding the impedance ZL of the reactance circuits itself, ideally. Although R≠0 holds practically, it does not affect the basic principle of the present invention. As a specific example of the reactance circuit 102, a circuit element such as a capacitor, a inductor and a transmission line, a circuit where a plurality of same type items out of them are combined, a circuit where a plurality of different type items out of them are combined and the like are cited. In this specification, an appellation “circuit” is used for the “reactance circuit” even in the case where it is constituted of a single circuit element such as a case where the circuit is constituted of one capacitor, for example, due to the organic relation with the line 902.
It is necessary that N reactance circuits 102 severally take the same or substantially the same reactance value. Herein, the reason why “substantially the same” reactance value should be enough, in other words, setting N reactance circuits 102 to completely the same reactance value is not strictly requested as a design condition is as follows. The fact that the reactance values of N reactance circuits 102 are not completely the same causes a small deviation of the resonance frequency (in short, a desired resonance frequency cannot be sustained). However, the fact causes no problem practically since the deviation of the resonance frequency is absorbed into bandwidth. In the following, as a technical matter including this meaning, it is assumed that N reactance circuits 102 take the same reactance values.
The above-described conditions commonly apply to various reactance circuits 102 that will be described later. For this condition, although it is desirable that N reactance circuits 102 are all the same type, they may not necessarily be reactance circuits of the same type as long as it is possible to achieve the condition that the same reactance value is taken as described above. Herein, description will be made by allocating the same reference numeral 102 to the reactance circuits on the assumption that this content is included.
[Variable Resonator]
N reactance circuits 102 are connected electrically to the line 902 as branching circuits at equal intervals based on the electrical length at a resonance frequency whose one wavelength or integral multiple thereof corresponds to the circumference of the line 902 regarding the circumference direction of the line 902. In actual designing, the resonance frequency whose one wavelength or integral multiple thereof corresponds to the circumference of the line 902 should only be the resonance frequency of the variable resonator 900 to which no reactance circuit 102 is connected, for example. However, although description will be made in detail later, it must be noted that the resonance frequency of the variable resonator 100a, where the reactance value of each reactance circuit is not infinity, is different from the resonance frequency of the variable resonator 900. In the case where the relative permittivity of the dielectric substrate 905 is uniform, the equal electrical length intervals match equal intervals based on the physical length. In such a case and when the line 902 is a circular shape, N reactance circuits 102 are connected to the line 902 at intervals where each central angle formed by the center O of the line 902 and each connection point of adjacent arbitrary reactance circuits 102 becomes an angle obtained by dividing 360 degrees by N (refer to
Note that the connection points of the switches 903 to the line 902 are set such that desired bandwidths can be obtained. Therefore, connecting the switch 903 to a position where the reactance circuit 102 is connected is allowed.
In the variable resonator 100b, M reactance circuits 102 (M is an even number of 4 or larger) are electrically connected to the line 902 as branching circuits. In more details, at the resonance frequency whose one wavelength or integral multiple thereof corresponds to the circumference of the line 902, M/2−1 the reactance circuits 102 are connected clockwise along the circumference direction at the intervals of equal electrical lengths from a certain position K1 arbitrarily set on the line 902 to a position K2 half the electrical length of the full loop of the line 902. It is to be noted that the equal electrical length intervals here mean equal electrical length intervals on the condition that the reactance circuits 102 are not provided on the position K1 and the position K2. Similarly, M/2−1 reactance circuits 102 out of the remaining reactance circuits 102 are connected counter-clockwise along the circumference direction at the intervals of equal electrical length from the position K1 to the position K2. It is to be noted that the equal electrical length intervals here also mean equal electrical length intervals on the condition that the reactance circuits 102 are not provided on the position K1 and the position K2 as described above. Then, the remaining two reactance circuits 102 are connected to the position K2. Herein, it is assumed that “clockwise” and “counter-clockwise” refer to circling directions when seen from the front of page surface of the drawings (the same applies below). Similar to the variable resonator 100a, in actual design, the resonance frequency whose one wavelength or integral multiple thereof corresponds to the circumference of the line 902 should be the resonance frequency of the variable resonator 900 to which no reactance circuit 102 is connected, for example. However, although description will be made in detail later, it must be noted that the resonance frequency of the variable resonator 100b where the reactance value of each reactance circuit is not infinity is different from the resonance frequency of the variable resonator 900.
In the case where the relative permittivity of the dielectric substrate 905 is uniform, the equal electrical length intervals match the equal intervals based on the physical length. In such a case, from the certain position K arbitrarily set on the line 902 (corresponding to position K1) to a position half the circumference L of the line 902 along the circumference direction of the line 902 (corresponding to position K2), M/2 reactance circuits 102 are connected at positions remote from the position K by the distance of (L/M)×m (m is an integer satisfying 1≦m≦M/2) clockwise along the line 902. Similarly, from the position K to the position half the circumference L of the line 902 along the circumference direction of the line 902 (corresponding to position K2), the remaining M/2 reactance circuits 102 are connected at positions remote from the position K by the distance of (L/M)×m (m is an integer satisfying 1≦m≦M/2) counter-clockwise along the line 902 In short, the reactance circuit 102 is not connected to the position K, but two reactance circuits 102 are connected to the position remote from the position K by the distance of (L/M)×M/2 clockwise or counter-clockwise along the line 902.
Particularly in the case where the line 902 is a circular shape, M reactance circuits 102 are connected to positions remote by m times an angle obtained by dividing 360 degrees by M from the certain position K arbitrarily set on the line 902 clockwise along the route of the line 902 and to positions remote from the position K by m times the angle obtained by dividing 360 degrees by M counter-clockwise along the route of the line 902, seen from the center O of the line 902 (refer to
It is necessary that all of the M reactance circuits 102 take the same or substantially the same reactance value. The meaning of “substantially the same” is as described above. However, the circuit configuration at the position where the two reactance circuits 102 are connected (corresponding to the above-described the position K2), that is, the portion shown by the dotted-line framed portion α of
In the description below and each drawings, for the convenience of description and illustration, description and illustration will be made based on the case where the electrical length is not influenced on the line 902, that is, the case where the equal electrical length intervals match the equal intervals based on the physical length. Not only technical characteristics understood from the drawings, technical characteristics made clear from the following description not only applies to the case where the equal electrical length intervals match the equal intervals based on the physical length, but also applies to the case where the reactance circuits 102 are at the above-described connection points based on the electrical length.
Regarding the above-described variable resonator 100a and variable resonator 100b, description will be made for a mechanism for changing bandwidth and a mechanism for changing resonance frequency by referring to
Since frequency characteristics of the variable resonator 100a and the variable resonator 100b are shown as circuit simulation results in
First, the mechanism for changing bandwidth will be described.
Although the details are written in Japanese Patent Application Number: 2006-244707, in the loop line body 101, that is, the variable resonator 900, the positions of transmission zeros that occur around a resonance frequency whose one wavelength or integral multiple thereof corresponds to the circumference of the line 902 can be moved by selecting a single switch 903 to be turned to a conduction state (hereinafter, also referred to an ON state). Herein, the transmission zero is a frequency where the transmission coefficient of the circuit where the input/output line 7 is connected to the loop line body 101 (Transmission Coefficient: unit is decibel [dB]) becomes minimum, that is, an insertion loss becomes maximum. Since a bandwidth is decided by the positions of the transmission zeros, the bandwidth of the loop line body 101 can be significantly changed in response to the selection of the switch 903 to be turned to the conduction state.
Further, by employing the loop line 902, the loop line body 101 has characteristics that the signal at the resonance frequency whose one wavelength or integral multiple thereof corresponds to the circumference of the circular line 902 is not influenced by the parasitic resistance and the parasitic reactance of the switches 903. For this reason, in the case where a bandpass filter is formed by using the variable resonator 900 provided with the switches 903 having parasitic resistance, for example, the insertion loss of the bandpass filter is not influenced by the resistance of the switch 903 at a resonance frequency being a passband, so that the insertion loss can be made smaller.
Next, description will be made for the relationship between the reactance value of the reactance circuit 102 and the resonance frequency.
According to the reference literature given below, by making a resonator having the constitution that a circular line 802 is cut at two positions symmetrical with respect to the center of the line and capacitors 10 being as the reactance circuits are inserted each in cut area, the resonance frequency of the resonator can be made different in response to the capacitance of each capacitor 10. Therefore, by applying the technology to the variable resonator 900 capable of significantly changing bandwidth, it seems to be possible to realize a variable resonator whose resonance frequency is determined corresponding to the reactance value while being capable of significantly changing bandwidth. However, even if the technology is applied to the variable resonator 900 capable of significantly changing bandwidth, it is impossible to realize the variable resonator whose resonance frequency is determined corresponding to the reactance value while being capable of significantly changing bandwidth. This will be described by using a variable resonator 850 where the technology is applied to the variable resonator 900 capable of significantly changing bandwidth (refer to
A thick line indicated by the sign of 10 degrees in
When the position of the switch 903 in the conduction state is changed from 10 degrees to 30 degrees in order to change only the bandwidth without changing the resonance frequency in a state where the switch 903 in the conduction state is placed at the 10-degree position to obtain a center frequency 5.0 GHz and a certain bandwidth with every capacitance of the inserted two capacitors 10 set to a certain value (1 pF in this example),
The inventors got a conception from the foregoing that three or more reactance circuits 102 were required in order to realize a variable resonator whose resonance frequency is determined corresponding to the reactance value while being capable of significantly changing bandwidth. Then, description will be made for the fact that three or more reactance circuits 102 are required by showing the frequency characteristics of the circuit simulations of the variable resonator 100a and the variable resonator 100b in the case where various numbers of the reactance circuits 102 are electrically connected to the line 902.
The arrangement and capacitance C of the capacitors in circuit simulation are as shown in
Each frequency characteristics shown by the circuit simulations is the transmission coefficient of a signal when the signal inputted from Port 1 is transmitted to Port 2, and it is expressed in a dB unit. The resonance frequency should be a frequency when the impedance of the variable resonator takes infinity, and it is a frequency when the insertion loss takes a minimum in the frequency characteristics shown in
“When the capacitance of each capacitor 10 is 0 pF, in other words, when the capacitors 10 are not connected, the length of the loop line 902 is set such that the frequency at which insertion loss takes a minimum becomes 5.0 GHz. When the capacitance of each capacitor 10 is continuously changed from 0 pF, the frequency at which the insertion loss takes a minimum continuously changes from 5 GHz to a lower frequency side in response to the change of the capacitance. A frequency at which the continuously changed insertion loss takes a minimum is the resonance frequency discussed here”.
Accompanying circuits such as the input/output port and the input/output line are similar to the circuits shown in
As it is clear from
The above description gives the findings that at least three reactance circuits 102 are necessary in order to prevent the resonance frequency from being influenced by selecting the switch 903 turned to be the conduction state in the variable resonator 100a and the variable resonator 100b. In the above description, the characteristic impedance of the loop line 902 of the variable resonator 100a or the variable resonator 100b was set to 50Ω same as that of the input/output line and the input/output port, it is not particularly limited to this, but is a design parameter decided corresponding to the performance/characteristics required.
Although the capacitor is used on behalf of the reactance circuits 102 in the above description, a similar effect is obtained when a circuit element such as an inductor and a transmission line, a circuit where a plurality of the same type items out of them are combined, a circuit where a plurality of different type items out of them are combined or the like is used instead of the capacitor.
Herein, description will be made for the effect that a change of the resonance frequency of the variable resonator by a reactance circuit such as a capacitor and an inductor from a resonance frequency which is determined by the length of a loop line gives to the size of a variable resonator.
First, description will be made for the case where a capacitive reactance circuit, e.g. a capacitor, is loaded as a reactance circuit. Referring to
Next, description will be made for the case where an inductive reactance circuit, e.g. an inductor, is loaded as a reactance circuit. In the constitution similar to
As described above, since the bandwidth can be significantly changed in response to the selection of the switch 903 to be turned to the ON state, and the circumference of the line 902 is set so as to achieve a desired resonance frequency based on the correlation with each reactance value of each reactance circuit 102, the variable resonator can be manufactured in an arbitrary size by appropriately designing the reactance circuit 102.
One ends of the transmission lines 12 are connected to the line 902, and the other ends of the transmission lines 12 are open-circuited. However, leaving the other ends of the transmission lines 12 open is not an essential technical matter, but may be grounded, for example.
The constitution of the reactance circuit 102 is the same as that of the reactance circuit 102 in the variable resonator 100e shown in
In the above-described the variable resonator 100a and the same type structure thereof, a connected portion between the input/output line 7 and the variable resonator 100a, that is, a supply point of a signal is at the center of the two reactance circuits 102 sandwiching the supply point, but a position off from the center may be set as a supply point of a signal as shown in
In the above-described the variable resonator 100a and the same type structure thereof, each reactance circuit 102 is electrically connected to the loop line 902 as a branching circuit, but as shown in
Similarly, in the above-described the variable resonator 100b and the same type structure thereof, each reactance circuit 102 is electrically connected to the circular line 902 as a branching circuit, but as shown in
In each drawing, the circumference of the loop line before cutting is the same as the sum of the lengths of the fragment lines after cutting in both cases. In the example shown in
Connection points of the switches 903 to the line 902 are set such that a desired bandwidth is obtained, and the connection points sustain without change even in each cut line after cutting. Therefore, one or more fragment lines to which no switch 903 is connected may exist.
From a different perspective, each variable resonator shown in
Similarly, from a different perspective, the variable resonator shown in
Particularly in the variable resonator 100b which employed the constitution of series connection shown in
Hereinafter, when either the variable resonator 100a or the same type structure thereof or the variable resonator 100b or the same type structure thereof is acceptable, reference numeral 100 allocated and the resonator will be called a variable resonator 100.
In addition, without inserting the variable phase shifter 700, a tunable bandwidth filter is also acceptable in which the positions where the variable resonators 100 are connected to the input/output line 7 are connected by a line of quarter wavelength at the resonance frequency of the variable resonator 100.
[1] Two single-pole r-throw switches 77 are provided where r is an integer of 2 or larger, both r-throw side terminals select the same one transmission line out of r transmission lines 181 to 18r whose lengths are different and thus signal phase between ports (R1, R2) is made variable (refer to
[2] Two or more variable capacitors 19 are connected along the transmission line 18, and the end portion of the variable capacitors 19 on the opposite side of the end portion which are connected to the transmission line 18 are grounded. By appropriately changing the capacitance of each variable capacitor 19 as a design matter, a signal phase between the ports (R1, R2) is made variable (refer to
[3] Two or more switches 20 are connected along the transmission line 18, and the end portions of the switches 20 on the opposite side of the end portions which are connected to the transmission line 18 are connected to a transmission line 21. By appropriately changing the conduction state of each switch 20 as a design matter, a signal phase between the ports (R1, R2) is made variable (refer to
[4] By appropriately changing the capacitance of the variable capacitor 19 between the ports (R1, R2) as a design matter, a signal phase between the ports (R1, R2) is made variable (refer to
[5] The variable capacitor 19 is connected to the input/output line 7 between the ports (R1, R2) as a branching circuit. An end portion of the variable capacitor 19 on the opposite side of the end portion, which is connected to the input/output line 7 is grounded. By appropriately changing the capacitance of the variable capacitor 19 as a design matter, a signal phase between the ports (R1, R2) is made variable (refer to FIG. 23).
[6] By appropriately changing the inductance of a variable inductor 11 between ports (R1, R2) as a design matter, a signal phase between ports (R1, R2) is made variable (refer to
[7] The variable inductor 11 is connected to the input/output line 7 between the ports (R1, R2). An end portion of the variable inductor 11 on the opposite side of the end portion, which is connected to the input/output line 7 is grounded. By appropriately changing the inductance of the variable inductor 11 as a design matter, a signal phase between the ports (R1, R2) is made variable (refer to
Although the above-described each tunable bandwidth filter bused two or more variable resonators 100, it is possible to constitute the tunable bandwidth filter by using single variable resonator 100. In constituting the tunable bandwidth filter by using one variable resonator 100, the filter becomes as exemplified in
The above-described tunable bandwidth filter has the constitution that a single signal supply point at which the variable resonator 100 is connected to the input/output line 7 exsits 1, and the variable resonator 100 is connected to the input/output line 7 as a branching circuit. However, as shown in
The frequency characteristics of the tunable bandwidth filter 400 employing the constitution is shown in
As described above, at least three reactance circuits 102 of the variable resonator 100 are necessary. From the viewpoint of miniaturization, it seems to be preferable that the number of the reactance circuits 102 is as small as possible. However, a constitution provided with a large number of the reactance circuits 102 has an advantage, and it will be described by employing the case of using capacitors as an example.
Referring to
Further, description will be made for an effect produced by the fact that the resonance frequency of the variable resonator 100 changes by the reactance circuits 102 such as the capacitor, the inductor and the transmission lines from a resonance frequency, which is determined by the length of the circular line 902.
Not limited to the variable resonator 100, there are cases where the relative permittivity of a substrate for fabricating a resonator is not constant among substrates or even in the same substrate depending on the conditions in manufacturing the resonator despite the same material and the same manufacturing method. For this reason, even if resonators having the same dimensions are formed on the substrate, the phenomenon occurs that the resonance frequencies of the resonators are different. Therefore, there are cases where adjustment work is required in a general filter using a resonator. In a resonator using a transmission line, adjusting the resonance frequency by trimming the length of the transmission lie is generally done, but it is impossible for the resonator provided with the loop line. Further, although adjusting the resonance frequency by adding a reactance element such as a capacitor is also generally done, such an adjustment method is not versatile depending on the design environment of resonator. In a resonator capable of significantly changing only the bandwidth at a certain center frequency, adjustment cannot be performed by adding the reactance element without thorough consideration in many cases. Under the existing circumstances, the variable resonator 100 can enjoy advantageous effect. For example, in the case where no reactance circuit 102 is connected, if the variable resonator 100 designed to resonate at a resonance frequency being a design value resonates at a higher frequency than the design resonance frequency due to a lower relative permittivity of the actual substrate than the relative permittivity of a substrate used during designing, the frequency can be easily adjusted to the design resonance frequency by connecting the reactance circuit 102 having an appropriate reactance value to the variable resonator 100. Then, the change of the position of the switch 903 to be turned to the conduction state does not influence resonance frequency in the variable resonator 100.
Hereinafter, description will be made for a modified example according to an embodiment of the present invention.
Regarding the variable resonator 100, by turning the switch 903 to the ON state which is at a position w times (w=0, 1, 2, 3, . . . ) the electrical length π at the design resonance frequency from the signal supply point along the line 902, input impedance at the signal supply point can be brought to 0. Therefore, in the case of constituting the tunable bandwidth filter by using the variable resonator 100, a signal of the design resonance frequency is prevented from passing the filter by turning the switch 903 to the ON state which is at a position w times the electrical length π at the design resonance frequency. On the other hand, by turning the switch 903 at the position to the OFF state, the signal of the design resonance frequency is allowed to pass the filter. Then, when the tunable bandwidth filter is constituted not aiming at signal elimination but passing the signal of a desired frequency, there is no need to provide the switches 903 at the positions of integral multiple of the electrical length π in the design resonance frequency. As shown in
When the switch 903 at the position w times the electrical length π at the design resonance frequency from the signal supply point along the line 902 at the design resonance frequency is not turned to the ON state, input impedance in the signal supply point can be brought to infinity in the variable resonator 100. For this reason, characteristics having a low insertion loss is obtained even if the switch 903 of a relatively large resistance is used as shown in
Thus, a constitution positively utilizing resistors may be also employed. For example, the case of positively utilizing resistors such as switching the case where the line 902 is connected to the ground conductor 904 directly by a switch 35 being a switching device having a low resistance and the case where the line 902 is connected to the ground conductor 904 by the switch 35 via a resistor 70 having several ohms to several tens ohms which is higher than the resistance of the switch 35, are possible (refer to
Although the case of using resistors has been shown here, not limited to the resistor, a passive element exemplified by a variable resistor, an inductor, a variable inductor, a capacitor, a variable capacitor, a piezoelectric element and the like, for example, may be used.
It is possible to constitute a tunable bandwidth filter by executing electrical connection between the variable resonator 100 and the transmission line 30 based on electric field coupling or magnetic field coupling.
A tunable bandwidth filter 404 shown in
In the case of the tunable bandwidth filter 404, selecting of the switches (33, 34) realizes a state where only one variable resonator 100X is connected or the other state where both of the variable resonators 100X are connected. The resonance frequencies are the same in both states, whereas frequency characteristics are different in each state. When both of the variable resonators 100X are connected to the input/output line 7, an attenuation amount of a signal at a frequency further from the resonance frequency becomes larger comparing to the case of connecting only one variable resonator 100X to the input/output line 7. This is because the characteristic impedance of the variable resonators 100X becomes half equivalently. In short, the characteristic impedance of each variable resonator to the input/output line 7 is switched by changing the ON or OFF state of the switches (33, 34), and the frequency characteristics of the tunable bandwidth filter 404 can be changed corresponding to the two states above.
In the case of the tunable bandwidth filter 405, selecting of the switches (33, 34) realizes three states: a first state where only one variable resonator X is connected, a second state where only one variable resonator Y is connected and a third state where both of the variable resonators (X, Y) are connected. The resonance frequencies are the same in all states, whereas frequency characteristics are different in each state. In short, in the tunable bandwidth filter 405, the characteristic impedance of each variable resonator to the input/output line 7 is switched by changing the ON or OFF state of the switches (33, 34) similar to the case of the tunable bandwidth filter 404, and the frequency characteristics of the tunable bandwidth filter 404 can be changed corresponding to the three states above.
Although the tunable bandwidth filter 400 shown in
All of the variable resonators 100 shown above are in the circular shape, but the present invention is not intended particularly to the circular shape. The essence of the present invention is in [1] constituting the variable resonator in a loop shape (refer to
Generally, low insertion loss can be obtained by the constitution shown in
Further, if a multilayer structure is allowed, the constitution shown in
Description will be added to several modes of the multilayer structure by referring to the cross-sectional views along the line XI-XI in the visual line direction shown in
A first example of the multilayer structure should have the constitution that the ground conductor 904 being the lowest layer and the dielectric substrate 905 being the upper layer thereof are arranged in a contacted manner, and furthermore, the dielectric substrate 905 and the transmission line 7a being the upper layer thereof are arranged in a contacted manner as shown in
A second example of the multilayer structure should have the constitution that the ground conductor 904 being the lowest layer and the dielectric substrate 905 being the upper layer thereof are arranged in a contacted manner, and furthermore, the dielectric substrate 905 and the loop line 902 on the upper layer thereof are arranged in a contacted manner as shown in
A third example of the multilayer structure should have the constitution that the ground conductor 904 being the lowest layer and the dielectric substrate 905 being the upper layer thereof are arranged in a contacted manner, and furthermore, the dielectric substrate 905 and the transmission line 7b and conductors 331 which are on the upper layer of the substrate are arranged in a contacted manner as shown in
A fourth example of the multilayer structure should have the constitution that the ground conductor 904 being the lowest layer and the dielectric substrate 905 being the upper layer thereof are arranged in a contacted manner, and furthermore, the dielectric substrate 905 and the transmission line 7b on the upper layer thereof are arranged in a contacted manner as shown in
A fifth example of the multilayer structure should have the constitution that the ground conductor 904 being the lowest layer and the dielectric substrate 905 being the upper layer thereof are arranged in a contacted manner, and furthermore, the dielectric substrate 905 and the transmission line 7a and the loop line 902 which are on an upper layer of the dielectric substrate 905 are arranged in a contacted manner as shown in
A sixth example of the multilayer structure should have the constitution that the ground conductor 904 being the lowest layer and the dielectric substrate 905 being the upper layer thereof are arranged in a contacted manner, and furthermore, the dielectric substrate 905 and the transmission line 7a and the loop line 902, which are on an upper layer of the dielectric substrate 905 are arranged in a contacted manner as shown in
Further, as shown in
In view of the convenience or the like of a circuit constitution provided with a plurality of variable resonators, a constitution with a connection between the variable resonator and the transmission line as shown in
Further, as a modified example of the constitution of the connection shown in
A low insertion loss can be obtained by the constitution shown in
This is because, in addition to the fact that a positional relation between the transmission line 7 and the line 902 of the variable resonator is remote, the line 902 has an exceedingly short line portion approximately parallel with the transmission line 7 in the vicinity of a connection area between the transmission line 7 and the line 902 in the case of the constitution shown in
Further, the foregoing embodiments are shown by using the microstrip line structure, but the present invention is not intended to limit it to such a line structure, and other line structures such as a coplanar waveguide may be used.
| Number | Date | Country | Kind |
|---|---|---|---|
| 2007-042786 | Feb 2007 | JP | national |
This application is a divisional of U.S. application Ser. No. 12/035,108, filed Feb. 21, 2008, now issued as U.S. Pat. No. 8,324,988, the entire content of which is incorporated herein by reference, and is based upon and claims the benefit of priority under 35 U.S.C. 119 from prior Japanese Patent Application No. 2007-042786, filed Feb. 22, 2007.
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| Number | Date | Country | |
|---|---|---|---|
| 20130057363 A1 | Mar 2013 | US |
| Number | Date | Country | |
|---|---|---|---|
| Parent | 12035108 | Feb 2008 | US |
| Child | 13665316 | US |
