This disclosure relates to a self-biased current source that combines a very low minimum supply voltage with a very high maximum supply voltage without danger of oxide damage.
Bandgap reference voltage circuits are used to provide stable reference voltages over wide variations in operating temperatures. A common bandgap reference voltage circuit 100 is shown in
The amplifier 104 driving the voltage vgcore settles when both inputs of the amplifier 104 are at the same voltage. This occurs when the drop across resistor R1 in
Icore*R1=νt*ln(k) (1)
The voltage vbg has a zero temperature coefficient when
Icore*R2+Vdiodekx≅1.26V (2)
One of the start-up circuit's 102 functions is to ensure that the bandgap circuit 100 does not remain at a zero-current stable state. To avoid a zero-current stable state, the start-up circuit 102 is provided to initialize the loop, then is effectively removed to avoid an offset error after the bandgap circuit 100 has stabilized.
Embodiments of the invention address these and other limitations in the prior art.
This startup circuit 102, however, assumes that the current Istart is smaller than the current Icore of the bandgap circuit 202, and therefore requires a large resistor Rstart, typically several Megohms. Furthermore, even when startup circuit 102 is off, current continues to flow in Rstart. Therefore, although this startup circuit 102 has a good minimum supply requirement, the startup circuit 102 has poor supply stability, overall power consumption, and area characteristics.
An alternative startup circuit 300 is shown in
The gate of the pmos transistor 404 is connected to its own drain and also to the drain of the high voltage transistor 408 and the gate of transistor 410. The gate of transistor 408 is connected to voltage vgcore from the bandgap reference circuit 100. The source of the transistor 408 is connected to the source of the transistor 410 through supply voltage vdd. The start-up current Istart is then supplied through the drain of the transistor 410.
Start-up circuit 400 has no zero-current state, but requires more resistance at R4 compared to R3 in the previous circuit 300, since current Iref equals the gate source voltage Vgs, instead of δVgs, divided by R4. For typical maximum supply requirements, e.g. greater than 1.2V, all transistors in circuit 400 must be high-voltage types, which have correspondingly large Vth, further increasing the typical value of R4. Start-up circuit 400 also requires a sizable resistor R5 to bias the leftmost branch of the start-up circuit 400. Current Tamp through resistor R5 is supply voltage-dependent, although current Istart is not. The minimum supply requirement for current Tamp is approximately two times the threshold voltage of the nmos transistor 406. Thus, this current generator has most of the disadvantages of the startup circuit 102 discussed above and shown in
The start-up circuit 500 shown in
The gate of the pmos transistor 508 is also connected to the gate of transistor 510 and the drain of transistor 512. The gate of transistor 512 is connected to voltage vgcore from the bandgap reference circuit 100. The source of the transistor 512 is connected to the supply voltage vdd. The start-up current Istart is then supplied through the drain of the transistor 510. In one embodiment of circuit 500, typical sizes for these PMOS transistors are W/L=8 um/1 um.
A native transistor with the gate and source shorted, such as transistor 504, behaves as an ordinary transistor would with its gate to source voltage Vgs near its threshold voltage Vth, i.e., its current is roughly constant and its output resistance is high. Furthermore, for such a native transistor, current begins to flow at a drain to source voltage Vds of nearly 0V. Self-biased current sources may be made such as the one formed by transistor 504 in the left-most branch of
However, the start-up circuit 500 of
Native transistors may also be used in the feedback branch driving resistor R5, as discussed above. In this feedback branch, the native transistor 506 serves exactly the same purpose as the counterpart transistor 406 in
Furthermore, the drain to source voltage Vds of the amplifier transistor 502 is constrained to equal its gate to source voltage Vgs, which results in an improvement in supply range due to the native nmos feedback device, since the native transistor 504's Vgs is nominally 0V. Therefore it is safe to use a low-voltage transistor 502 for the amplifier, even for a large supply voltage vdd. Resistor R6 may be smaller for the same reference current, since the voltage across resistor R6 is the gate to source voltage of the transistor 502. A constraint to accommodate large supply voltages is that high-voltage pmos transistors must be used for the output mirror, and if no native pmos devices are available, the pmos threshold voltage Vth can degrade the minimum supply voltage. Even so, by applying the native transistors to a standard current reference design, large improvements in minimum supply voltage, bias current supply variation, and bias current overhead are made.
As used herein, the terms “about,” “substantially,” and “approximately,” may indicate a range of values within +/−5% of a stated value. As one example of process capability, the high voltage transistors discussed above have a threshold voltage Vth of approximately 600 mV, and may operate safely with up to 3.6V across any two of their terminals. The low-voltage transistors discussed above have Vth of approximately 550 mV and may operate safely with up to 1.4V across any two of their terminals. With these example transistors, R6 may be, for example. 1.5 megohms. Further, the native transistors are nmos transistors. However, other applications may use pmos native transistors in the above-discussed circuits.
It will be appreciated that several of the above-disclosed and other features and functions, or alternatives thereof, may be desirably combined into many other different systems or applications. Also that various presently unforeseen or unanticipated alternatives, modifications, variations, or improvements therein may be subsequently made by those skilled in the art which are also intended to be encompassed by the following claims.
This application is a continuation-in-part of co-pending U.S. Non-provisional patent application Ser. No. 15/078,894, filed Mar. 23, 2016, entitled “WIDE SUPPLY RANGE PRECISION STARTUP CURRENT SOURCE,” the disclosure of which is incorporated herein by reference in its entirety.
Number | Name | Date | Kind |
---|---|---|---|
5084665 | Dixon et al. | Jan 1992 | A |
6002242 | Migliavacca | Dec 1999 | A |
6351178 | Ooishi | Feb 2002 | B1 |
6509855 | Cable | Jan 2003 | B1 |
6853164 | Prinz et al. | Feb 2005 | B1 |
7531999 | Chang | May 2009 | B2 |
8013588 | Imura | Sep 2011 | B2 |
20060038550 | Nazarian | Feb 2006 | A1 |
20060044053 | Tang et al. | Mar 2006 | A1 |
20060197584 | Hsu | Sep 2006 | A1 |
20070164722 | Rao | Jul 2007 | A1 |
20070194770 | Kalyanaraman | Aug 2007 | A1 |
20080231248 | Hung | Sep 2008 | A1 |
20100164609 | Yoo | Jul 2010 | A1 |
20100181987 | Sicard | Jul 2010 | A1 |
20100278002 | Chen et al. | Nov 2010 | A1 |
20110006749 | Stellberger et al. | Jan 2011 | A1 |
20110050197 | Yuasa | Mar 2011 | A1 |
20110127989 | Hikichi et al. | Jun 2011 | A1 |
20110169561 | Chu | Jul 2011 | A1 |
20140312875 | Nascimento | Oct 2014 | A1 |
20170131736 | Acar et al. | May 2017 | A1 |
Number | Date | Country |
---|---|---|
2273339 | Jan 2011 | EP |
2767976 | Mar 1999 | FR |
Entry |
---|
International Search Report and Written Opinion issued in International Application No. PCT/US2017/023891, dated Jun. 21, 2017, 12 pages. |
Number | Date | Country | |
---|---|---|---|
20180232000 A1 | Aug 2018 | US |
Number | Date | Country | |
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Parent | 15078894 | Mar 2016 | US |
Child | 15955620 | US |