BACKGROUND OF THE INVENTION
It is desirable to reduce an antenna's sidelobe or grating lobe nulling. Typical phased array antennas utilize a single radiating mode, and in order to reduce the sidelobes, apply phase tapers or adjust the amplitude. There is a limit to how much nulling can be achieved through the use of tapers. There is a need for an improved antenna with reduced sidelobe and grating lobe nulling.
SUMMARY
Disclosed herein is a wideband dual-mode antenna comprising a dielectric substrate and a conductive layer. The conductive layer is disposed on a first face of the dielectric substrate. Two tapered slots are formed in the conductive layer and are separated from each other by a linear center conductor also formed in the conductive layer. The tapered slots narrow to slot-lines terminated by respective baluns at a feed end of the wideband dual-mode antenna. The two slot-lines follow paths that, at the feed end, transition from being parallel to the center conductor to following meandering paths that curve away from, and then back towards, the center conductor.
An embodiment of the wideband dual-mode antenna is disclosed herein as comprising a dielectric substrate, a conductive layer, two micro-strip conductors, and a conductive isolation boundary. The dielectric substrate has first and second faces that are opposite to each other. The conductive layer is disposed on the first face and two tapered slots are formed in the conductive layer. Each tapered slot tapers from a mouth at an aperture end to a slot-line at a feed end. A center conductor is also formed in the conductive layer separating the two tapered slots. The micro-strip conductors are disposed on the second face so as to feed the two tapered slots to form tapered slot antennas. The conductive isolation boundary is disposed on the second face opposite the center conductor and electrically connected to the center conductor through a series of vias in the dielectric substrate.
An embodiment of the wideband dual-mode antenna is disclosed herein as comprising a dielectric substrate, a conductive layer, two micro-strip conductors, and a conductive isolation boundary. The dielectric substrate has first and second faces that are opposite to each other and the conductive layer is disposed on the first face. Two tapered slots are formed in the conductive layer so that each tapered slot tapers from a mouth at an aperture end to a slot-line at a feed end. The two micro-strip conductors are disposed on the second face so as to feed the two tapered slots to form tapered slot antennas. The conductive isolation boundary is disposed on the second face so as to be between the two tapered slots and is electrically connected to the conductive layer.
BRIEF DESCRIPTION OF THE DRAWINGS
Throughout the several views, like elements are referenced using like references. The elements in the figures are not drawn to scale and some dimensions are exaggerated for clarity.
FIG. 1A is a top-view illustration of an embodiment of a wideband dual-mode antenna.
FIG. 1B is an expanded, perspective-view illustration of the embodiment of the wideband dual-mode antenna shown in FIG. 1A.
FIG. 2 is a plot of data.
FIG. 3 is a prior art image of a dual-mode tapered slot antenna.
FIG. 4A is a top-view illustration of an embodiment of a wideband dual-mode antenna.
FIG. 4B is an expanded, perspective-view illustration of the embodiment of the wideband dual-mode antenna shown in FIG. 4A.
FIG. 5A is a perspective-view illustration of an embodiment of a wideband dual-mode antenna.
FIG. 5B is a top-view of a conductive layer of the embodiment of the wideband dual-mode antenna of FIG. 5A.
FIG. 5C is a top-view of a dielectric layer of the embodiment of the wideband dual-mode antenna of FIG. 5A.
FIG. 5D is a top-view of micro-strip feeds and an isolation boundary of the embodiment of the wideband dual-mode antenna of FIG. 5A.
FIG. 6 is a schematic view of a hybrid coupler.
FIG. 7A is an illustration of common mode and differential mode cross-polar and co-polar radiation patterns of an embodiment of the wideband dual-mode antenna at 4 GHz.
FIG. 7B is an illustration of common mode and differential mode cross-polar and co-polar radiation patterns of an embodiment of the wideband dual-mode antenna at 16 GHz.
FIG. 8 is a plot of data.
FIG. 9 is an illustration depicting the 3D radiation patterns of common and differential radiating modes for an embodiment of the wideband, dual-mode antenna.
DETAILED DESCRIPTION OF EMBODIMENTS
The disclosed antenna below may be described generally, as well as in terms of specific examples and/or specific embodiments. For instances where references are made to detailed examples and/or embodiments, it should be appreciated that any of the underlying principles described are not to be limited to a single embodiment, but may be expanded for use with any of the other methods and systems described herein as will be understood by one of ordinary skill in the art unless otherwise stated specifically.
FIGS. 1A and 1B are illustrations of an embodiment of a wideband dual-mode antenna 10 that comprises, consists of, or consists essentially of a dielectric substrate 12 and a conductive layer 14. FIG. 1A is a top-view of the embodiment of the wideband dual-mode antenna 10 and FIG. 1B is an expanded, perspective-view of the embodiment. The conductive layer 14 is disposed on a first face 16 of the dielectric substrate 12. Two tapered slots 18a and 18b are formed in the conductive layer 14 such that they are separated from each other by a linear center conductor 20 that is also formed in the conductive layer 14. The center conductor may be aligned with a center line 25 of the wideband dual-mode antenna 10. The tapered slots 18a and 18b transition to slot-lines 22a and 22b that are terminated by respective baluns 24a and 24b at a feed end 26 of the wideband dual-mode antenna 10. As shown in FIGS. 1A and 1B, in this embodiment of the wideband, dual-mode antenna 10, the two slot-lines 22a and 22b follow paths that, at the feed end 26, transition from being parallel to the center conductor 20 to following meandering paths that curve away from, and then back towards, the center conductor 20. In FIG. 1A, the dielectric substrate 12 is transparent to facilitate viewing of the alignment of the conductive layer 14 with respect to two micro-strip conductors 28a and 28b that are disposed on a second face 30 of the dielectric substrate 12 at the feed end 26. The two micro-strip conductors 28a and 28b are configured to feed the two tapered slots 18a and 18b to form tapered slot antennas at an aperture end 32.
The wideband, dual-mode antenna 10 can support multiple radiating modes and can be used in beamforming arrays to reduce and mitigate sidelobes or grating lobes or both. FIGS. 1A and 1B illustrate a Vivaldi, or tapered slot, embodiment of the wideband, dual-mode antenna 10 that includes two transitions from two micro-strip conductors 28a and 28b to two slot-lines 22a and 22b slot-line transitions within the aperture opening of the Vivaldi antenna. The wideband, dual-mode antenna 10 may be configured to simultaneously generate a differential radiating mode and a common mode where the patterns for each of the modes are orthogonal.
FIG. 2 is a plot showing the broadside (zenith) gain versus frequency for the common and differential radiating modes of an embodiment of the wideband, dual-mode antenna 10. For the common mode, there is a destructive cosine pattern, with a null at zenith. For the differential mode, there is a constructive pattern, with a peak at zenith. As can be seen in FIG. 2, the two radiating modes are broadband and have a large separation between the modes. The larger the separation between the modes, the less interaction they'll have with each other.
FIG. 3 is a top-view illustration of a prior art example of a wideband phased array antenna with grating lobe cancellation from the paper “A Wideband Phased Array Antenna with Grating Lobe Cancellation” by Jia-Chi Samuel Chieh, Sanghamitro Das, and Satish K. Sharma, presented at the 2021 IEEE International Symposium on Antennas and Propagation and USNC-URSI Radio Science Meeting, which paper is incorporated herein by reference. For modal combination, the higher the isolation between the two modes, the better the nulling capability you can achieve for both sidelobe and grating lobe nulling. The embodiment of the wideband, dual-mode antenna 10 shown in FIGS. 1A and 1B increases the isolation between the modes beyond the isolation achieved by the prior art by meandering the slot line transition (i.e., in this case the meandering path includes three 90-degree curves) so that the two slot-lines 22a and 22b have a larger physical separation than the phased array antenna shown in FIG. 3.
FIGS. 4A and 4B are illustrations of an embodiment of a wideband dual-mode antenna 10 that further comprises an isolation boundary 34. FIG. 4A is a top-view of the embodiment of the wideband dual-mode antenna 10 and FIG. 4B is an expanded, perspective-view of the embodiment. The isolation boundary 34 is conductive, is disposed on the second face 20 of the dielectric substrate 12, and is electrically connected to the center conductor 20. The isolation boundary 34 helps increase the isolation between the two radiating modes. In the embodiment of the wideband dual-mode antenna 10 shown in FIGS. 4A and 4B, the isolation boundary 34 has approximately the same dimensions as the center conductor 20 and is electrically connected to the center conductor 20 by a plurality of evenly-spaced vias 36 in the dielectric substrate 12 that may be filled with the same conductive material from which the isolation boundary is made.
FIG. 5A is a perspective view of an embodiment of the wideband dual-mode antenna 10 comprising the meandering slot-line paths (22a and 22b) as well as the isolation boundary 34. FIGS. 5B, 5C, and 5D are respectively top views of the conductive layer 14, the dielectric substrate 12, and the micro-strip conductors or feeds 28a and 28b corresponding to the embodiment of the wideband dual-mode antenna 10 shown in FIG. 5A. As with FIG. 1A, the dielectric substrate 12 appears as transparent or invisible in FIG. 5 so as to facilitate viewing of the conductive layer 14.
FIG. 6A is a schematic illustration of a 90-degree hybrid coupler 38 connected to the two micro-strip conductors 28a and 28b such that the corresponding tapered slot antennas generate two orthogonal radiation patterns, such that one of the two tapered slot antennas (e.g., the one fed by micro-strip conductor 28a) operates in a common mode and the other tapered slot antenna (e.g., the one fed by micro-strip conductor 28b) operates in a differential mode. When the wideband dual-mode antenna 10 is excited in-phase, or in the common mode, since it has two feeds (i.e., micro-strip conductors 28a and 28b) a difference pattern may be obtained. When the wideband dual-mode antenna 10 is excited out of phase by 180°, or in the differential mode, then a summation pattern may be obtained. One can generate both of these patterns by using a 90° hybrid coupler. The hybrid coupler 38 may be used to generate the sum and difference beams in a similar fashion to how sum and differences beam are generated in a monopulse feed system. However, with the wideband, dual-mode antenna 10, the sum and difference ports are arrayed.
FIGS. 7A and 7B are illustrations of common mode and differential mode cross-polar and co-polar radiation patterns at 4 GHz and 16 GHz respectively for the embodiment of the wideband, dual-mode antenna 10 shown in FIGS. 5A-5D. As can be seen, the common mode pattern is destructive with a null at zenith, and the differential mode pattern is constructive with a peak at zenith. These two radiating modes can be combined in a array configuration to reduce and mitigate sidelobes and/or grating lobes.
FIG. 8 is a plot of data showing the isolation between the co-polar common mode and the co-polar differential mode across frequency for the embodiment of the wideband, dual-mode antenna 10 shown in FIGS. 5A-5D. As one can see, there is great improvement by adding the isolation vias and by meandering the slotline feed. FIG. 9 is an illustration depicting the 3D radiation patterns of the common radiating mode and the differential radiating mode for the embodiment of the wideband, dual-mode antenna 10 shown in FIGS. 5A-5D
From the above description of the wideband, dual-mode antenna 10, it is manifest that various techniques may be used for implementing the concepts of the wideband, dual-mode antenna 10 without departing from the scope of the claims. The described embodiments are to be considered in all respects as illustrative and not restrictive. The method/apparatus disclosed herein may be practiced in the absence of any element that is not specifically claimed and/or disclosed herein. It should also be understood that the wideband, dual-mode antenna 10 is not limited to the particular embodiments described herein, but is capable of many embodiments without departing from the scope of the claims.
Patent Application
20250158288
