Patent Application
20160013659
The present invention relates to a wireless power transmission apparatus capable of adjusting power to be supplied by means of wireless power transmission, and a supply power control method and a manufacturing method for the wireless power transmission apparatus.
Portable electronic devices such as laptop PCs, tablet PCs, digital cameras, mobile phones, portable gaming devices, earphone-type music players, RF headsets, hearing aids, recorders, which are portable while being used by the user are rapidly increasing in recent years. Many of these portable electronic devices have therein a rechargeable battery, which requires periodical charging. To facilitate the work for charging the rechargeable battery of an electronic device, there are an increasing number of devices for charging rechargeable batteries by using a power-supplying technology (wireless power transmission technology performing power transmission by varying the magnetic field) that performs wireless power transmission between a power-supplying device and a power-receiving device mounted in an electronic device.
For example, as a wireless power transmission technology, there have been known, for example, a technology that performs power transmission by means of electromagnetic induction between coils (e.g. see PTL 1), a technology that performs power transmission by means of resonance phenomenon (magnetic field resonant state) between resonators (coils) provided to the power-supplying device and the power-receiving device (e.g. see PTL 2).
To stably charge a rechargeable battery by using such a wireless power transmission technology, the value of the power (current) supplied to the rechargeable battery needs to be within a predetermined range. This is because, when the power (current) supplied to the rechargeable battery falls short of a value within the predetermined range, the power is a small power (small current) which is insufficient for charging the rechargeable battery due to the characteristics of the rechargeable battery. On the other hand, the power (current) supplied to the rechargeable battery exceeding a value within the predetermined range causes an overcurrent which leads to heat generation in the rechargeable battery and the charging circuit, consequently shortening the life of the rechargeable battery and the charging circuit.
A conceivable approach to meet the above-described requirement is to control the power (current) to be supplied to the rechargeable battery so it is within a predetermined range of values by controlling the input impedance in a power-supplying device and a power-receiving device in which wireless power transmission takes place.
To control the input impedance of the power-supplying device and the power-receiving device in which wireless power transmission takes place, it is conceivable to provide the power-receiving device with an impedance matching box separately (e.g., see PTL 3).
However, separately providing an impedance matching box to a power-receiving device and the like causes an increase in the number of components, and is inconvenient in portable electronic devices for which portability, compactness, and cost-efficiency are required.
In other words, it is preferable that controlling of the input impedance is possible without an additional device to the power-supplying device and the power-receiving device which perform wireless power transmission.
In view of the above, an object of the present invention is to provide a wireless power transmission apparatus in which its input impedance is adjustable by means of adjustment of the coupling coefficient between coils provided in a power-supplying device and a power-receiving device which perform wireless power transmission, thereby enabling control of power (current) supplied, without a need of an additional device, and to provide a supply power control method and manufacturing method for such a wireless power transmission apparatus.
An aspect of the present invention to achieve the above object is a supply power control method for a wireless power transmission apparatus configured to supply power from a power-supplying module comprising at least one of a power-supplying coil and a power-supplying resonator to a power-receiving module comprising at least one of a power-receiving resonator and a power-receiving coil, while varying a magnetic field, wherein: the power-supplying coil, the power-supplying resonator, the power-receiving resonator, and the power-receiving coil each has at least one coil; and power to be supplied is adjusted by setting an input impedance of the wireless power transmission apparatus, by means of adjusting a value of coupling coefficient between coils next to each other.
With the above method, the power to be supplied is adjustable by setting an input impedance of the wireless power transmission apparatus, by means of adjusting a value of coupling coefficient between coils next to each other, in the power-supplying coil, the power-supplying resonator, the power-receiving resonator, and the power-receiving coil. This way, by setting the value of the input impedance of the wireless power transmission apparatus, the power to be supplied at the time of wireless power transmission is adjustable without a need of an additional device. In other words, control of power to be supplied is possible without a need of an additional component in the wireless power transmission apparatus.
Another aspect of the present invention to achieve the above object is a supply power control method for a wireless power transmission apparatus configured to supply power from a power-supplying module comprising at least a power-supplying coil and a power-supplying resonator to a power-receiving module comprising at least a power-receiving resonator and a power-receiving coil, by means of a resonance phenomenon, wherein the input impedance of the wireless power transmission apparatus is adjusted by adjusting at least one of a coupling coefficient k12 between the power-supplying coil and the power-supplying resonator, a coupling coefficient k23 between the power-supplying resonator and the power-receiving resonator, and a coupling coefficient k34 between the power-receiving resonator and the power-receiving coil.
The above method enables setting of input impedance of the wireless power transmission apparatus, by adjusting the coupling coefficient k12 between the power-supplying coil and the power-supplying resonator, the coupling coefficient k23 between the power-supplying resonator and the power-receiving resonator, and the coupling coefficient k34 between the power-receiving resonator and the power-receiving coil, thereby enabling control of the supplied power in the wireless power transmission apparatus configured to supply power by means of resonance phenomenon from the power-supplying module to the power-receiving module.
Another aspect of the present invention to achieve the above object is a supply power control method for a wireless power transmission apparatus, adapted so that the values of the coupling coefficients k12, k23, and k34 are adjusted by varying at least one of a distance between the power-supplying coil and the power-supplying resonator, a distance between the power-supplying resonator and the power-receiving resonator, and a distance between power-receiving resonator and the power-receiving coil.
With the above method, the value of the coupling coefficient k12 is varied by varying the distance between the power-supplying coil and the power-supplying resonator, the value of the coupling coefficient k23 is varied by varying the distance between the power-supplying resonator and the power-receiving resonator, and the value of the coupling coefficient k34 is varied by varying the distance between the power-receiving resonator and the power-receiving coil. Thus, it is possible to vary the values of coupling coefficients between coils, simply by physically varying the distance between the power-supplying coil and the power-supplying resonator, the distance between the power-supplying resonator and the power-receiving resonator, and the distance between the power-receiving resonator and the power-receiving coil. In other words, it is possible to adjust the input impedance in a wireless power transmission apparatus thereby enabling control of the power output from the wireless power transmission apparatus, simply by physically varying the distance between the power-supplying coil and the power-supplying resonator, the distance between the power-supplying resonator and the power-receiving resonator, and the distance between the power-receiving resonator and the power-receiving coil.
Another aspect of the present invention to achieve the above object is a supply power control method for a wireless power transmission apparatus, wherein the adjustment is based on a characteristic such that, if the distance between the power-supplying resonator and the power-receiving resonator, and the distance between the power-receiving resonator and the power-receiving coil are fixed, the power supplied by the resonance phenomenon is such that, the value of the coupling coefficient k12 between the power-supplying coil and the power-supplying resonator increases with a decrease in the distance between the power-supplying coil and the power-supplying resonator, and the value of the input impedance of the wireless power transmission apparatus increases with the increase in the value of the coupling coefficient k12.
With the above method, if the distance between the power-supplying resonator and the power-receiving resonator and the distance between the power-receiving resonator and the power-receiving coil are fixed, the value of the coupling coefficient k12 between the power-supplying coil and the power-receiving resonator is increased with a decrease in the distance between the power-supplying coil and the power-supplying resonator. Increasing the value of the coupling coefficient k12 raises the value of the input impedance in the wireless power transmission apparatus. To the contrary, by increasing the distance between the power-supplying coil and the power-supplying resonator, the value of the coupling coefficient k12 between the power-supplying coil and the power-supplying resonator is reduced. Reduction of the value of the coupling coefficient k12 reduces the value of the input impedance in the wireless power transmission apparatus. In other words, the above described supply power control method for a wireless power transmission apparatus, utilizing the above described characteristic enables adjustment of the input impedance in a wireless power transmission apparatus thereby enabling control of the power output from the wireless power transmission apparatus, simply by physically varying the distance between the power-supplying coil and the power-supplying resonator.
Another aspect of the present invention to achieve the above object is a supply power control method for a wireless power transmission apparatus, wherein the adjustment is based on a characteristic such that, if the distance between the power-supplying coil and the power-supplying resonator, and the distance between the power-supplying resonator and the power-receiving resonator are fixed, the power supplied by the resonance phenomenon is such that, the value of the coupling coefficient k34 between the power-receiving resonator and the power-receiving coil increases with a decrease in the distance between the power-receiving resonator and the power-receiving coil, and the value of the input impedance of the wireless power transmission apparatus decreases with the increase in the value of the coupling coefficient k34.
With the above method, if the distance between the power-supplying coil and the power-supplying resonator and the distance between the power-supplying resonator and the power-receiving resonator are fixed, the value of the coupling coefficient k34 between the power-receiving resonator and the power-receiving coil is increased with a decrease in the distance between the power-receiving resonator and the power-receiving coil. Increasing the value of the coupling coefficient k34 reduces the value of the input impedance in the wireless power transmission apparatus. To the contrary, by increasing the distance between the power-receiving resonator and the power-receiving coil, the value of the coupling coefficient k34 between the power-receiving resonator and the power-receiving coil is reduced. Reduction of the value of the coupling coefficient k34 raises the value of the input impedance in the wireless power transmission apparatus. In other words, the above described supply power control method for a wireless power transmission apparatus, utilizing the above described characteristic enables adjustment of the input impedance in a wireless power transmission apparatus thereby enabling control of the power output from the wireless power transmission apparatus, simply by physically varying the distance between the power-receiving resonator and the power-receiving coil.
Another aspect of the present invention to achieve the above object is a supply power control method for a wireless power transmission apparatus, wherein a transmission characteristic with respect to a driving frequency of the power supplied to the power-supplying module has a peak occurring in a drive frequency band lower than a resonance frequency of the power-supplying module and the power-receiving module, and in a drive frequency band higher than the resonance frequency, and the driving frequency of the power supplied to the power-supplying module is in a band corresponding to a peak value of the transmission characteristic occurring in a driving frequency band lower than the resonance frequency.
With the method described above, when the transmission characteristic with respect to a driving frequency of the power supplied to the power-supplying module is set so as to have a peak occurring in a drive frequency band lower than a resonance frequency of the power-supplying module and the power-receiving module, and in a drive frequency band higher than the resonance frequency, a relatively high transmission characteristic is ensured by setting the driving frequency of the power supplied to the power-supplying module in a band corresponding to a peak value of the transmission characteristic occurring in a driving frequency band lower than the resonance frequency.
By setting the power-source frequency of the power source to a frequency on the low frequency side, the current in the power-supplying resonator and the current in the power-receiving resonator flow in the same direction. With this, as the magnetic field occurring on the outer circumference side of the power-supplying module and the magnetic field occurring on the outer circumference side of the power-receiving module cancel each other out, the influence of the magnetic fields on the outer circumference sides of the power-supplying module and the power-receiving module is restrained, and the magnetic field space having a smaller magnetic field strength than a magnetic field strength in positions other than the outer circumference sides of the power-supplying module and the power-receiving module is formed. By placing, within the magnetic field space, circuits and the like which should be away from the influence of the magnetic field, it is possible to efficiently utilize a space, and downsize the wireless power transmission apparatus itself.
Another aspect of the present invention to achieve the above object is a supply power control method for a wireless power transmission apparatus, adapted so that, a transmission characteristic with respect to a driving frequency of the power supplied to the power-supplying module has a peak occurring in a drive frequency band lower than a resonance frequency of the power-supplying module and the power-receiving module, and in a drive frequency band higher than the resonance frequency, and the driving frequency of the power supplied to the power-supplying module is in a band corresponding to a peak value of the transmission characteristic occurring in a driving frequency band higher than the resonance frequency.
With the method described above, when the transmission characteristic with respect to a driving frequency of the power supplied to the power-supplying module is set so as to have a peak occurring in a drive frequency band lower than a resonance frequency of the power-supplying module and the power-receiving module, and in a drive frequency band higher than the resonance frequency, a relatively high transmission characteristic is ensured by setting the driving frequency of the power supplied to the power-supplying module in a band corresponding to a peak value of the transmission characteristic occurring in a driving frequency band higher than the resonance frequency.
Further, as the magnetic field occurring on the inner circumference side of the power-supplying module and the magnetic field occurring on the inner circumference side of the power-receiving module cancel each other out, the influence of the magnetic fields on the inner circumference sides of the power-supplying module and the power-receiving module is restrained, and the magnetic field space having a smaller magnetic field strength than a magnetic field strength in positions other than the inner circumference sides of the power-supplying module and the power-receiving module is formed. By placing, within the magnetic field space, circuits and the like which should be away from the influence of the magnetic field, it is possible to efficiently utilize a space, and downsize the wireless power transmission apparatus itself.
Another aspect of the present invention is a wireless power transmission apparatus adjusted by the above-described supply power control method for a wireless power transmission apparatus.
With the above structure, by setting the value of the input impedance of the wireless power transmission apparatus, the power to be supplied at the time of wireless power transmission is adjustable without a need of an additional device. In other words, control of power to be supplied is possible without a need of an additional component in the wireless power transmission apparatus.
Another aspect of the present invention to achieve the above object is a manufacturing method for a wireless power transmission apparatus configured to supply power from a power-supplying module comprising at least one of a power-supplying coil and a power-supplying resonator to a power-receiving module comprising at least one of a power-receiving resonator and a power-receiving coil, while varying a magnetic field, comprising the steps of: providing at least one coil in each of the power-supplying coil, the power-supplying resonator, the power-receiving resonator, and the power-receiving coil; and adjusting power to be supplied by setting an input impedance of the wireless power transmission apparatus, by means of adjusting a value of coupling coefficient between coils next to each other.
The above method enables manufacturing of a wireless power transmission apparatus in which the power to be supplied at the time of wireless power transmission is adjustable without a need of an additional device, by setting the value of the input impedance of the wireless power transmission apparatus. In other words, manufacturing of a wireless power transmission apparatus capable of controlling power to be supplied is possible without a need of an additional component in the wireless power transmission apparatus.
There is provided a wireless power transmission apparatus in which its input impedance is adjustable by means of adjustment of the coupling coefficient between coils provided in a power-supplying device and a power-receiving device which perform wireless power transmission, thereby enabling control of power (current) supplied, without a need of an additional device, and to provide a supply power control method and manufacturing method for such a wireless power transmission apparatus.
The following describes an embodiment of a wireless power transmission apparatus, a supply power control method and a manufacturing method for the wireless power transmission apparatus related to the present invention.
First, the following describes a wireless power transmission apparatus 1 designed and manufactured by the supply power control method and the manufacturing method, before describing the supply power control method and the manufacturing method themselves for the wireless power transmission apparatus.
The wireless power transmission apparatus 1 includes a power-supplying module 2 having a power-supplying coil 21 and a power-supplying resonator 22 and a power-receiving module 3 having a power-receiving coil 31 and the power-receiving resonator 32, as shown in
The power-supplying coil 21 plays a role of supplying power obtained from the AC power source 6 to the power-supplying resonator 22 by means of electromagnetic induction. As shown in
The power-receiving coil 31 plays roles of receiving the power having been transmitted as a magnetic field energy from the power-supplying resonator 22 to the power-receiving resonator 32, by means of electromagnetic induction, and supplying the power received to the rechargeable battery 9 via the stabilizer circuit and the charging circuit 8. As shown in
As shown in
In the RLC circuit which is the resonance circuit in each of the power-supplying resonator 22 and the power-receiving resonator 32, the resonance frequency is f which is derived from (Formula 1) below, where the inductance is L and the capacity of capacitor is C. In the present embodiment, the resonance frequency of the power-supplying coil 21, the power-supplying resonator 22, the power-receiving coil 31, and the power-receiving resonator 32 is set to 12.8 MHz.
The power-supplying resonator 22 and the power-receiving resonator 32 are each a 4-turn solenoid coil of a copper wire material (coated by insulation film), with its coil diameter being 96 mmφ. The resonance frequency of the power-supplying resonator 22 and that of the power-receiving resonator 32 are matched with each other. The power-supplying resonator 22 and the power-receiving resonator 32 may be a spiral coil or a solenoid coil as long as it is a resonator using a coil.
In regard to the above, the distance between the power-supplying coil 21 and the power-supplying resonator 22 is denoted as d12, the distance between the power-supplying resonator 22 and the power-receiving resonator 32 is denoted as d23, and the distance between the power-receiving resonator 32 and the power-receiving coil 31 is denoted as d34 (see
Further, as shown in
The resistance values, inductances, capacities of capacitors, and coupling coefficients K12, K23, and K34 of R1, L1, and C1 of the RLC circuit of the power-supplying coil 21, R2, L2, and C2 of the RLC circuit of the power-supplying resonator 22, R3, L3, and C3 of the RLC circuit of the power-receiving resonator 32, and R4, L4, and C4 of the RLC circuit of the power-receiving coil 31 are parameters variable at the stage of designing and manufacturing, and are preferably set so as to satisfy the relational expression of (Formula 3) which is described later.
With the wireless power transmission apparatus 1, when the resonance frequency of the power-supplying resonator 22 and the resonance frequency of the power-receiving resonator 32 match with each other, a magnetic field resonant state is created between the power-supplying resonator 22 and the power-receiving resonator 32. When a magnetic field resonant state is created between the power-supplying resonator 22 and the power-receiving resonator 32 by having these resonators resonating with each other, power is transmitted from the power-supplying resonator 22 to the power-receiving resonator 32 as magnetic field energy.
The following describes a supply power control method for adjusting the power supplied from the wireless power transmission apparatus 1, based on the structure of the wireless power transmission apparatus 1.
The (Formula 2) is a relational expression of the current Iin, based on the voltage Vin and input impedance Zin.
When supplying power from the wireless power transmission apparatus 1 of the present embodiment to the rechargeable battery 9, the value of the current Iin needs to be within a proper current range (Iin(MIN) to Iin (max)) as shown in
To control the current Iin to be within the proper current range (Iin(MIN) to Iin(MAX)) for the reasons stated above, the value of the input impedance Zin needs to be adjusted to be within a range of Zin(MIN) to Zin(MAX) as shown in
To be more specific about the input impedance Zin of the wireless power transmission apparatus 1, the structure of the wireless power transmission apparatus 1 is expressed in an equivalent circuit as shown in
Further, the impedance Z1, Z2, Z3, Z4, and Z1 of the power-supplying coil 21, the power-supplying resonator 22, the power-receiving resonator 32, and the power-receiving coil 31 in the wireless power transmission apparatus 1 of the present embodiment are expressed as the (Formula 4).
Introducing the (Formula 4) into the (Formula 3) makes the (Formula 5).
The resistance values, inductances, capacities of capacitors, and coupling coefficients K12, K23, and K34 of R1, L1, and C1 of the RLC circuit of the power-supplying coil 21, R2, L2, and C2 of the RLC circuit of the power-supplying resonator 22, R3, L3, and C3 of the RLC circuit of the power-receiving resonator 32, R4, L4, and C4 of the RLC circuit of the power-receiving coil 31 are used as parameters variable at the stage of designing and manufacturing, to adjust the value of the input impedance Zin of the wireless power transmission apparatus 1 derived from the above (Formula 5) to be within the range of Zin(MIN) to Zin(MAX).
(Control of Input Impedance Zin with Coupling Coefficients)
It is generally known that, in the above described wireless power transmission apparatus, the power transmission efficiency of the wireless power transmission is maximized by matching the driving frequency of the power supplied to the power-supplying module 2 to the resonance frequencies of the power-supplying coil 21 and the power-supplying resonator 22 of the power-supplying module and the power-receiving coil 31 and the power-receiving resonator 32 of the power-receiving module 3. The driving frequency is therefore set to the resonance frequency generally to maximize the power transmission efficiency. It should be noted that the power transmission efficiency is a rate of power received by the power-receiving module 3, relative to the power supplied to the power-supplying module 2.
Thus, to maximize the power transmission efficiency in the wireless power transmission apparatus 1, it is necessary to satisfy capacity conditions and resonance conditions of the capacitors and coils (ωL=1/ωC) so that the driving frequency matches with the resonance frequency of the RLC circuits of the power-supplying module 2 and the power-receiving module 3.
Specifically, when the input impedance Zin of the wireless power transmission apparatus 1 satisfying the resonance condition (ωL=1/ωC) which maximizes the power transmission efficiency in the wireless power transmission apparatus 1 to the (Expression 5), the expression will be: (ωL1−1/ωC1=0), (ωL2−1/ωC2=0), (ωL3−1/ωC3=0), and (ωL4−1/ωC4=0), and the relational expression (Expression 6) is derived.
From the above relational expression (Formula 6), it should be understood that the resistance values such as R1 of the RLC circuit of the power-supplying coil 21, R2 of the RLC circuit of the power-supplying resonator 22, R3 of the RLC circuit of the power-receiving resonator 32, R4 of the RLC circuit of the power-receiving coil 31, and the coupling coefficients K12, K23, and K34 are only the main variable parameters to adjust the value of the input impedance Zin of the wireless power transmission apparatus 1 within the range of Zin(MIN) to Zin(MAX).
When the driving frequency of the power supplied to the power-supplying module 2 is matched with the resonance frequency to maximize the power transmission efficiency in the wireless power transmission apparatus 1, the coupling coefficients k12, k23, and k34 are usable as the parameters for controlling the value of the input impedance Zin in the wireless power transmission apparatus 1 so that it is within the range of Zin(MIN) to Zin(MAX).
Further, as hereinabove described, when the driving frequency of the power supplied to the power-supplying module 2 is not matched with the resonance frequency of the power-supplying resonator 22 of the power-supplying module 2 and the power-receiving resonator 32 of the power-receiving module 3 (ωL≈1/ωC), the coupling coefficients k12, k23, and k34 are usable as the parameters for controlling the value of the input impedance Zin in the wireless power transmission apparatus 1 so that it falls within the range of Zin(MIN) to Zin(MAX).
Next, with reference to measurement experiments 1 to 6, the following describes how the input impedance Zin of the wireless power transmission apparatus 1 varies, with variations in the coupling coefficients k12, k23, and k34.
In the measurement experiments 1 to 6, the wireless power transmission apparatus 1 shown in
In the Measurement Experiments are used a wireless power transmission apparatus 1 with a double-hump transmission characteristic “S21” relative to the driving frequency of the power supplied to the wireless power transmission apparatus 1.
Transmission characteristic “S21” herein is a signal value measured by a network analyzer 110 connected to the wireless power transmission apparatus 1, and is indicated in decibel. The greater the value, the higher the power transmission efficiency. The transmission characteristic “S21” of the wireless power transmission apparatus 1 relative to the driving frequency of the power supplied to the wireless power transmission apparatus 1 may have either single-hump or double-hump characteristic, depending on the strength of coupling (magnetic coupling) by the magnetic field between the power-supplying module 2 and the power-receiving module 3. The single-hump characteristic means the transmission characteristic “S21” relative to the driving frequency has a single peak which occurs in the resonance frequency band (fo) (See dotted line 51
In a wireless power transmission apparatus 1 having the single-hump characteristic, the transmission characteristic “S21” is maximized (power transmission efficiency is maximized) when the driving frequency is at the resonance frequency f0, as indicated by the dotted line 51 of
On the other hand, in a wireless power transmission apparatus 1 having the double-hump characteristic, the transmission characteristic “S21” is maximized in a driving frequency band (fL) lower than the resonance frequency fo, and in a driving frequency band (fH) higher than the resonance frequency fo, as indicated by the solid line 52 of
It should be noted that, in general, if the distance between the power-supplying resonator and the power-receiving resonator is the same, the maximum value of the transmission characteristic “S21” having the double-hump characteristic (the value of the transmission characteristic “S21” at fL or fH) is lower than the value of the maximum value of the transmission characteristic “S21” having the single-hump characteristic (value of the transmission characteristic “S21” at f0) (See graph in
Specifically, in cases of double-hump characteristic, when the driving frequency of the AC power to the power-supplying module 2 is set to the frequency fL nearby the peak on the low frequency side (inphase resonance mode), the power-supplying resonator 22 and the power-receiving resonator 32 are resonant with each other in inphase, and the current in the power-supplying resonator 22 and the current in the power-receiving resonator 32 both flow in the same direction. As the result, as shown in the graph of
Further, in the inphase resonance mode, because the magnetic field generated on the outer circumference side of the power-supplying resonator 22 and the magnetic field generated on the outer circumference side of the power-receiving resonator 32 cancel each other out, the magnetic field spaces each having a lower magnetic field strength than the magnetic field strengths in positions not on the outer circumference sides of the power-supplying resonator 22 and the power-receiving resonator 32 (e.g., the magnetic field strengths on the inner circumference sides of the power-supplying resonator 22 and the power-receiving resonator 32) are formed on the outer circumference sides of the power-supplying resonator 22 and the power-receiving resonator 32, as the influence of the magnetic fields is lowered. When a stabilizer circuit 7, a charging circuit 8, a rechargeable battery 9, or the like desired to have less influence of the magnetic field is placed in this magnetic field space, occurrence of Eddy Current attributed to the magnetic field is restrained or prevented. This restrains negative effects due to generation of heat.
On the other hand, in cases of double-hump characteristic, when the driving frequency of the AC power to the power-supplying module 2 is set to the frequency fH nearby the peak on the side of the high frequency side (antiphase resonance mode), the power-supplying resonator 22 and the power-receiving resonator 32 resonate with each other in antiphase, and the current in the power-supplying resonator 22 and the current in the power-receiving resonator 32 flow opposite directions to each other. As the result, as shown in the graph of
Further, in the antiphase resonance mode, because the magnetic field generated on the inner circumference side of the power-supplying resonator 22 and the magnetic field generated on the inner circumference side of the power-receiving resonator 32 cancel each other out, the magnetic field spaces each having a lower magnetic field strength than the magnetic field strengths in positions not on the inner circumference side of the power-supplying resonator 22 and the power-receiving resonator 32 (e.g., the magnetic field strengths on the outer circumference side of the power-supplying resonator 22 and the power-receiving resonator 32) are formed on the outer circumference sides of the power-supplying resonator 22 and the power-receiving resonator 32, as the influence of the magnetic fields is lowered. When a stabilizer circuit 7, a charging circuit 8, a rechargeable battery 9, and the like desired to have less influence of the magnetic field is placed in this magnetic field space, occurrence of Eddy Current attributed to the magnetic field is restrained or prevented. This restrains negative effects due to generation of heat. Further, since the magnetic field space formed in this antiphase resonance mode is formed on the inner circumference side of the power-supplying resonator 22 and the power-receiving resonator 32, assembling the electronic components such as the stabilizer circuit 7, the charging circuit 8, the rechargeable battery 9, and the like within this space makes the wireless power transmission apparatus 1 itself more compact, and improves the freedom in designing.
(Measurement Experiment 1: Variation in Input Impedance Zin when Coupling Coefficient k12 is Varied)
In the wireless power transmission apparatus 1 used in the measurement experiment 1, the power-supplying coil 21 is constituted by an RL circuit (non-resonating) including a resistor R1 and a coil L1. The coil L1 is a single-turn coil of a copper wire material (coated by an insulation film) with its coil diameter set to 96 mmφ. Similarly, the power-receiving coil constitutes an RL circuit (non-resonating) including a resistor R4 and a coil L4. The coil L4 is a single-turn coil of a copper wire material (coated by an insulation film) with its coil diameter set to 96 mmφ. Further, the power-supplying resonator 22 is constituted by an RLC circuit including a resistor R2, a coil L2, and a capacitor C2, and adopts a 4-turn solenoid coil of a copper wire material (coated by an insulation film) with its diameter set to 96 mmφ. Further, the power-receiving resonator 32 is constituted by an RLC circuit including a resistor R3, a coil L3, and a capacitor C3, and adopts a 4-turn solenoid coil of a copper wire material (coated by an insulation film) with its diameter set to 96 mmφ. The values of R1, R2, R3, R4 in the wireless power transmission apparatus 1 used in Measurement Experiment 1 were set to 0.05Ω, 0.5Ω, 0.5Ω, and 0.05Ω, respectively. Further, the values of L1, L2, L3, L4 were set to 0.3 μH, 4 μH, 4 μH, and 0.3 μH, respectively. The resonance frequency of the power-supplying resonator 22 and that of the power-receiving resonator 32 was 12.8 MHz.
In the measurement experiment 1, the coupling coefficients k23 and k34 were fixed to 0.10 and 0.35, respectively, and while the value of the coupling coefficient k12 was changed among four values, i.e., 0.11Ω, 0.15Ω, 0.22Ω, and 0.35Ω, the value of the input impedance Zin of the wireless power transmission apparatus 1 with respect to the driving frequencies of the power supplied to the power-supplying module 2 was measured for four values of the variable resistor 11 (R1), i.e., 51Ω, 100Ω, 270Ω, and 500Ω(the method of adjusting the coupling coefficient is detailed later).
As should be seen in the measurement results in the inphase resonance mode shown in
Further, when the value of the variable resistor 11 (R1) is set to 100Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 33.1Ω->39.0Ω->54.8Ω->97.1 Ω.
Further, when the value of the variable resistor 11 (R1) is set to 270Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 37.8Ω->48.2Ω->76.0Ω->148.5 Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 40.9Ω->54.5Ω->90.1Ω->183.1Ω.
As should be understood from the above, in the inphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to rise with an increase in the coupling coefficient k12 in a sequence of 0.11->0.15->0.22->0.35, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500Ω.
Similarly, as should be seen in the measurement results in the antiphase resonance mode shown in
Further, when the value of the variable resistor 11 (R1) is set to 100Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 28.7Ω->29.4Ω->32.6Ω->50.3Ω.
Further, when the value of the variable resistor 11 (R1) is set to 270Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 30.7Ω->33.5Ω->43.0Ω->80.6 Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 31.8Ω->35.8Ω->49.1Ω->96.7 Ω.
As should be understood from the above, in the antiphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to rise with an increase in the coupling coefficient k12 in a sequence of 0.11->0.15->0.22->0.35, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500Ω.
(Measurement Experiment 2: Variation in Input Impedance Zin when Coupling Coefficient k12 is Varied)
In the wireless power transmission apparatus 1 used in the measurement experiment 2, unlike Measurement Experiment 1, the power-supplying coil 21 is constituted by an RLC circuit (resonating) including a resistor R1, a coil L1, and a capacitor C1. The coil L1 is a single-turn coil of a copper wire material (coated by an insulation film) with its coil diameter set to 96 mmφ. Similarly, the power-receiving coil 31 is constituted by an RLC circuit whose elements include a resistor R4, a coil L4, and a capacitor C4. The coil L4 is a single-turn coil of a copper wire material (coated by insulation film) with its coil diameter set to 96 mmφ. The other structures are the same as those in Measurement Experiment 1. The values of R1, R2, R3, R4 in the wireless power transmission apparatus 2 used in Measurement Experiment 2 were set to 0.05Ω, 0.5Ω, 0.5Ω, and 0.05Ω, respectively. Further, the values of L1, L2, L3, L4 were set to 0.3 μH, 4 μH, 4 μH, and 0.3 pH, respectively. The resonance frequency of the power-supplying coil 21, the power-supplying resonator 22, the power-receiving resonator 32, and the power-receiving coil 31 was 12.8 MHz.
In the measurement experiment 2, the coupling coefficients k23 and k34 were fixed to 0.10 and 0.35, respectively, and while the value of the coupling coefficient k12 was changed among four values, i.e., 0.11Ω, 0.15Ω, 0.22Ω, and 0.35Ω, the value of the input impedance Zin of the wireless power transmission apparatus 1 with respect to the driving frequencies of the power supplied to the power-supplying module 2 was measured for four values of the variable resistor 11 (R1), i.e., 51Ω, 100Ω, 270Ω, and 500Ω.
As should be seen in the measurement results in the inphase resonance mode shown in
Further, when the value of the variable resistor 11 (R1) is set to 100Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 10.0Ω->18.1Ω->35.4Ω->77.6 Ω.
Further, when the value of the variable resistor 11 (R1) is set to 270Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 17.3Ω->31.8Ω->62.2Ω->136.5 Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500 U and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 21.8Ω->40.3Ω->79.0Ω->173.1 Ω.
As should be understood from the above, in the inphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to rise with an increase in the coupling coefficient k12 in a sequence of 0.11->0.15->0.22->0.35, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500Ω.
Similarly, as should be seen in the measurement results in the antiphase resonance mode shown in
Further, when the value of the variable resistor 11 (R1) is set to 100Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 6.9Ω->9.5Ω->19.3Ω->49.8 Ω.
Further, when the value of the variable resistor 11 (R1) is set to 270Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 9.3Ω->14.9Ω->31.2Ω->79.0 Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 10.7Ω->18.0Ω->38.1Ω->95.9 Ω.
As should be understood from the above, in the antiphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to rise with an increase in the coupling coefficient k12 in a sequence of 0.11->0.15->0.22->0.35, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500Ω.
(Measurement Experiment 3: Variation in Input Impedance Zin when Coupling Coefficient k12 is Varied)
The wireless power transmission apparatus 1 used in Measurement Experiment 3, unlike Measurement Experiments 1 and 2, adopts a pattern coil formed by winding a coil in a planer manner on coil parts of the power-supplying coil 21, the power-supplying resonator 22, the power-receiving resonator 32, and the power-receiving coil 31. Further, the power-supplying coil 21 is constituted by an RLC circuit (resonating) whose elements include a resistor R1, a coil L1, and a capacitor C1. The coil L1 is a 12-turn pattern coil with its coil diameter set to 35 mmφ, which is formed by etching a copper foil. Further, the power-receiving coil 31 is constituted by an RLC circuit whose elements include a resistor R4, a coil L4, and a capacitor C4. The coil L4 is a 12-turn pattern coil with its coil diameter set to 35 mmφ, which is formed by etching a copper foil. Further, the power-supplying resonator 22 is constituted by an RLC circuit whose elements include a resistor R2, a coil L2, and a capacitor C2. The coil L2 is a 12-turn pattern coil with its coil diameter set to 35 mmφ, which is formed by etching a copper foil. Further, the power-receiving resonator 32 is constituted by an RLC circuit whose elements include a resistor R3, a coil L3, and a capacitor C3. The coil L3 is a 12-turn pattern coil with its coil diameter set to 35 mmφ, which is formed by etching a copper foil. The values of R1, R2, R3, R4 in the wireless power transmission apparatus 1 used in Measurement Experiment 3 were set to 1.8Ω, 1.8Ω, 1.8Ω, and 1.8Ω, respectively. Further, the values of L1, L2, L3, L4 were set to 2.5 μH, 2.5 μH, 2.5 μH, and 2.5 μH, respectively. The resonance frequency of the power-supplying coil 21, the power-supplying resonator 22, the power-receiving resonator 32, and the power-receiving coil 31 was 8.0 MHz.
In the measurement experiment 3, the coupling coefficients k23 and k34 were fixed to 0.05 and 0.08, respectively, and while the value of the coupling coefficient k12 was changed among four values, i.e., 0.05Ω, 0.06Ω, 0.07Ω, and 0.08Ω, the value of the input impedance Zin of the wireless power transmission apparatus 1 with respect to the driving frequencies of the power supplied to the power-supplying module 2 was measured for four values of the variable resistor 11 (R1), i.e., 51Ω, 100Ω, 270Ω, and 500Ω.
As should be seen in the measurement results in the inphase resonance mode shown in
Further, when the value of the variable resistor 11 (R1) is set to 100Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 10.5Ω->20.7Ω->34.1Ω->42.3 Ω.
Further, when the value of the variable resistor 11 (R1) is set to 270Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 12.3Ω->24.0Ω->39.8Ω->49.9 Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 12.8Ω->25.4Ω->41.9Ω->51.9 Ω.
As should be understood from the above, in the inphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to rise with an increase in the coupling coefficient k12 in a sequence of 0.05->0.06->0.07->0.08, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500Ω.
Similarly, as should be seen in the measurement results in the antiphase resonance mode shown in
Further, when the value of the variable resistor 11 (R1) is set to 100Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 9.5Ω->15.8Ω->26.6Ω->34.2 Ω.
Further, when the value of the variable resistor 11 (R1) is set to 270Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 10.5Ω->17.3Ω->29.4Ω->37.8Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500Ω and when the value of the coupling coefficient k12 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 rose as follows: 10.8Ω->18.0Ω->30.5Ω->38.7 Ω.
As should be understood from the above, in the antiphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to rise with an increase in the coupling coefficient k12 in a sequence of 0.05->0.06->0.07->0.08, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500Ω.
(Measurement Experiment 4: Variation in Input Impedance Zin when Coupling Coefficient k34 is Varied)
In the wireless power transmission apparatus 1 used in the measurement experiment 4, similarly to Measurement Experiment 1, the power-supplying coil 21 is constituted by an RL circuit (non-resonating) including a resistor R1 and a coil L1. The coil L1 is a single-turn coil of a copper wire material (coated by an insulation film) with its coil diameter set to 96 mmφ. Similarly, the power-receiving coil 31 constitutes an RL circuit (non-resonating) including a resistor R4 and a coil L4. The coil L4 is a single-turn coil of a copper wire material (coated by an insulation film) with its coil diameter set to 96 mmφ. The other structures are the same as those in Measurement Experiment 1. The values of R1, R2, R3, R4 in the wireless power transmission apparatus 4 used in Measurement Experiment 4 were set to 0.05Ω, 0.5Ω, 0.5Ω, and 0.05Ω, respectively. Further, the values of L1, L2, L3, L4 were set to 0.3 μH, 4 μH, 4 μH, and 0.3 μH, respectively (the same as Measurement experiment 1). The resonance frequency of the power-supplying resonator 22 and that of the power-receiving resonator 32 was 12.8 MHz.
In the measurement experiment 4, the coupling coefficients k12 and k23 were fixed to 0.35 and 0.10, respectively, and while the value of the coupling coefficient k12 was changed among four values, i.e., 0.11Ω, 0.15Ω, 0.22Ω, and 0.35Ω, the value of the input impedance Zin of the wireless power transmission apparatus 1 with respect to the driving frequencies of the power supplied to the power-supplying module 2 was measured for four values of the variable resistor 11 (R1), i.e., 51Ω, 100Ω, 270Ω, and 500Ω (the method of adjusting the coupling coefficient is detailed later).
As should be seen in the measurement results in the inphase resonance mode shown in
Further, when the value of the variable resistor 11 (R1) is set to 100 U and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 228.2Ω->197.7->152.8Ω->97.1Ω.
Further, when the value of the variable resistor 11 (R1) is set to 270Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 259.1Ω->242.0Ω->209.7Ω->148.5Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 269.2Ω->259.3Ω->230.2Ω->183.1Ω.
As should be understood from the above, in the inphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to decrease with an increase in the coupling coefficient k34 in a sequence of 0.11->0.15->0.22->0.35, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500 Ω.
Similarly, as should be seen in the measurement results in the antiphase resonance mode shown in
Further, when the value of the variable resistor 11 (R1) is set to 100Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 127.4Ω->112.8Ω->86.8Ω->50.3Ω.
Further, when the value of the variable resistor 11 (R1) is set to 270Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 138.0Ω->131.1Ω->115.0Ω->80.6Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 141.3Ω->137.6Ω->126.5Ω->96.7Ω.
As should be understood from the above, in the antiphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to decrease with an increase in the coupling coefficient k34 in a sequence of 0.11->0.15->0.22->0.35, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500 Ω.
(Measurement Experiment 5: Variation in Input Impedance Zin when Coupling Coefficient k34 is Varied)
In the wireless power transmission apparatus 1 used in the measurement experiment 5, unlike Measurement Experiment 4, the power-supplying coil 21 is constituted by an RLC circuit (resonating) including a resistor R1, a coil L1, and a capacitor C1. The coil L1 is a single-turn coil of a copper wire material (coated by an insulation film) with its coil diameter set to 96 mmφ. Similarly, the power-receiving coil 31 is constituted by an RLC circuit whose elements include a resistor R4, a coil L4, and a capacitor C4. The coil L4 is a single-turn coil of a copper wire material (coated by insulation film) with its coil diameter set to 96 mmφ. The other structures are the same as those in Measurement Experiment 4. The values of R1, R2, R3, R4 in the wireless power transmission apparatus 1 used in Measurement Experiment 5 were set to 0.05Ω, 0.5Ω, 0.5Ω, and 0.05Ω, respectively. Further, the values of L1, L2, L3, L4 were set to 0.3 μH, 4 μH, 4 μH, and 0.3 μH, respectively. The resonance frequency of the power-supplying coil 21, the power-supplying resonator 22, the power-receiving resonator 32, and the power-receiving coil 31 was 12.8 MHz.
In the measurement experiment 5, the coupling coefficients k12 and k23 were fixed to 0.35 and 0.10, respectively, and while the value of the coupling coefficient k34 was changed among four values, i.e., 0.11Ω, 0.15Ω, 0.22Ω, and 0.35Ω, the value of the input impedance Zin of the wireless power transmission apparatus 1 with respect to the driving frequencies of the power supplied to the power-supplying module 2 was measured for four values of the variable resistor 11 (R1), i.e., 51Ω, 100Ω, 270Ω, and 500Ω.
As should be seen in the measurement results in the inphase resonance mode shown in
Further, when the value of the variable resistor 11 (Rd) is set to 100Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 204.9Ω->176.5Ω->133.4Ω->77.6Ω.
Further, when the value of the variable resistor 11 (R1) is set to 270Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 238.0Ω->222.8Ω->193.8Ω->136.5Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 246.7Ω->239.7Ω->216.2Ω->173.1Ω.
As should be understood from the above, in the inphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to decrease with an increase in the coupling coefficient k34 in a sequence of 0.11->0.15->0.22->0.35, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500Ω.
Similarly, as should be seen in the measurement results in the antiphase resonance mode shown in
Further, when the value of the variable resistor 11 (R1) is set to 100Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 119.3Ω->105.2Ω->83.3Ω->49.8Ω.
Further, when the value of the variable resistor 11 (R1) is set to 270 U and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 130.6Ω->123.4Ω->110.9Ω->79.0Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500 U and when the value of the coupling coefficient k34 is raised in the sequence of 0.11->0.15->0.22->0.35, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 133.9Ω->129.3Ω->122.1Ω->95.9Ω.
As should be understood from the above, in the antiphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to decrease with an increase in the coupling coefficient k34 in a sequence of 0.11->0.15->0.22->0.35, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500Ω.
(Measurement Experiment 6: Variation in Input Impedance Zin when Coupling Coefficient k34 is Varied)
The wireless power transmission apparatus 1 used in Measurement Experiment 6, unlike Measurement Experiments 4 and 5, adopts a pattern coil formed by winding a coil in a planer manner on coil parts of the power-supplying coil 21, the power-supplying resonator 22, the power-receiving resonator 32, and the power-receiving coil 31. Further, the power-supplying coil 21 is constituted by an RLC circuit (resonating) whose elements include a resistor R1, a coil L1, and a capacitor C1. The coil L1 is a 12-turn pattern coil with its coil diameter set to 35 mmφ, which is formed by etching a copper foil. Further, the power-receiving coil 31 is constituted by an RLC circuit whose elements include a resistor R4, a coil L4, and a capacitor C4. The coil L4 is a 12-turn pattern coil with its coil diameter set to 35 mmφ, which is formed by etching a copper foil. Further, the power-supplying resonator 22 is constituted by an RLC circuit whose elements include a resistor R2, a coil L2, and a capacitor C2. The coil L2 is a 12-turn pattern coil with its coil diameter set to 35 mmφ, which is formed by etching a copper foil. Further, the power-receiving resonator 32 is constituted by an RLC circuit whose elements include a resistor R3, a coil L3, and a capacitor C3. The coil L3 is a 12-turn pattern coil with its coil diameter set to 35 mmφ, which is formed by etching a copper foil. The values of R1, R2, R3, R4 in the wireless power transmission apparatus 1 used in Measurement Experiment 6 were set to 1.8Ω, 1.8Ω, 1.8Ω, and 1.8Ω, respectively. Further, the values of L1, L2, L3, L4 were set to 2.5 μH, 2.5 μH, 2.5 μH, and 2.5 μH, respectively. The resonance frequency of the power-supplying coil 21, the power-supplying resonator 22, the power-receiving resonator 32, and the power-receiving coil 31 was 8.0 MHz.
In the measurement experiment 6, the coupling coefficients k12 and k23 were fixed to 0.08 and 0.05, respectively, and while the value of the coupling coefficient k34 was changed among four values, i.e., 0.05Ω, 0.06Ω, 0.07Ω, and 0.08Ω, the value of the input impedance Zin of the wireless power transmission apparatus 1 with respect to the driving frequencies of the power supplied to the power-supplying module 2 was measured for four values of the variable resistor 11 (R1), i.e., 51Ω, 100Ω, 270Ω, and 500Ω.
As should be seen in the measurement results in the inphase resonance mode shown in
Further, when the value of the variable resistor 11 (R1) is set to 100Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 59.7Ω->56.1Ω->51.4Ω->42.3Ω.
Further, when the value of the variable resistor 11 (Rd) is set to 270Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 62.6Ω->60.6Ω->58.6Ω->49.9Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 63.5Ω->62.0Ω->61.0Ω->51.9Ω.
As should be understood from the above, in the inphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to decrease with an increase in the coupling coefficient k34 in a sequence of 0.05->0.06->0.07->0.08, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500 Ω.
Similarly, as should be seen in the measurement results in the antiphase resonance mode shown in
Further, when the value of the variable resistor 11 (R1) is set to 100Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 45.6Ω->43.7Ω->41.2Ω->34.2Ω.
Further, when the value of the variable resistor 11 (R1) is set to 270Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 46.8Ω->45.7Ω->44.6Ω->37.8Ω.
Further, when the value of the variable resistor 11 (R1) is set to 500Ω and when the value of the coupling coefficient k34 is raised in the sequence of 0.05->0.06->0.07->0.08, the value of the input impedance Zin of the wireless power transmission apparatus 1 decreased as follows: 47.1Ω->46.2Ω->45.1Ω->38.7Ω.
As should be understood from the above, in the antiphase resonance mode, the value of the input impedance Zin of the wireless power transmission apparatus 1 tends to decrease with an increase in the coupling coefficient k34 in a sequence of 0.05->0.06->0.07->0.08, when the value of the variable resistor 11 (R1) is set to any of the following values 51Ω, 100Ω, 270Ω, or 500 Ω.
With the above Measurement Experiments 1 to 6, the power to be supplied is adjustable by setting an input impedance Zin of the wireless power transmission apparatus 1 by means of adjusting a value of coupling coefficient such as the coupling coefficients k12 and k34, between coils next to each other, in the power-supplying coil 21, the power-supplying resonator 22, the power-receiving resonator 32, and the power-receiving coil 31 provided in the wireless power transmission apparatus 1.
The following describes a method of adjusting the coupling coefficients k12, k23, and k34, which are each a parameter for controlling the input impedance Zin in the wireless power transmission apparatus 1.
In wireless power transmission, the relation between a coupling coefficient k and a distance between a coil and another coil is typically such that the value of the coupling coefficient k increases with a decrease in (shortening of) the distance between the coil and the other coil, as shown in
As should be understood from the measurement experiments for variation in the input impedance Zin due to variation in the coupling coefficient, with the above method for adjusting the coupling coefficient, if the distance d23 between the power-supplying resonator 22 and the power-receiving resonator 32 and the distance d34 between the power-receiving resonator 32 and the power-receiving coil 31 are fixed, the value of the coupling coefficient k12 between the power-supplying coil 21 and the power-supplying resonator 22 is increased with a decrease in the distance d12 between the power-supplying coil 21 and the power-supplying resonator 22. Increasing the value of the coupling coefficient k12 raises the value of the input impedance Zin in the wireless power transmission apparatus 1. To the contrary, by increasing the distance d12 between the power-supplying coil 21 and the power-supplying resonator 22, the value of the coupling coefficient k12 between the power-supplying coil 21 and the power-supplying resonator 22 is reduced. Reduction of the value of the coupling coefficient k12 lowers the value of the input impedance Zin in the wireless power transmission apparatus 1.
That is, the value of the input impedance Zin increases with a decrease in the distance d12 between the power-supplying coil 21 and the power-supplying resonator 22. Based on (Formula 2), the increase in the input impedance Zin reduces the current Iin in the wireless power transmission apparatus 1, thus controlling the power output from the wireless power transmission apparatus 1 to be small. To the contrary, the value of the input impedance Zin decreases with an increase in the distance d12 between the power-supplying coil 21 and the power-supplying resonator 22. Based on (Formula 2), the decrease in the input impedance Zin raises the current Iin in the wireless power transmission apparatus 1, thus controlling the power output from the wireless power transmission apparatus 1 to be large.
In other words, the above described supply power control method for a wireless power transmission apparatus 1, utilizing the above described characteristic enables adjustment of the input impedance Zin in a wireless power transmission apparatus 1 thereby enabling control of the power output from the wireless power transmission apparatus 1, simply by physically varying the distance d12 between the power-supplying coil 21 and the power-supplying resonator 22.
Further, if the distance d12 between the power-supplying coil 21 and the power-supplying resonator 22 and the distance d23 between the power-supplying resonator 22 and the power-receiving resonator 32 are fixed, the value of the coupling coefficient k34 between the power-receiving resonator 32 and the power-receiving coil 31 increases with a decrease in the distance d34 between the power-receiving resonator 32 and the power-receiving coil 31. Increasing the value of the coupling coefficient k34 reduces the value of the input impedance Zin in the wireless power transmission apparatus 1. To the contrary, by increasing the distance d34 between the power-receiving resonator 32 and the power-receiving coil 31, the value of the coupling coefficient k34 between the power-receiving resonator 32 and the power-receiving coil 31 is reduced. Reduction of the value of the coupling coefficient k34 raises the value of the input impedance Zin in the wireless power transmission apparatus 1.
That is, the value of the input impedance Zin decreases with a decrease in the distance d34 between the power-receiving resonator 32 and the power-receiving coil 31. Based on (Formula 2), the decrease in the input impedance Zin raises the current Iin in the wireless power transmission apparatus 1, thus controlling the power output from the wireless power transmission apparatus 1 to be large. To the contrary, the value of the input impedance Zin increases with an increase in the distance d34 between the power-receiving resonator 32 and the power-receiving coil 31. Based on (Formula 2), the increase in the input impedance Zin reduces the current Iin in the wireless power transmission apparatus 1, thus controlling the power output from the wireless power transmission apparatus 1 to be small.
In other words, the above described supply power control method for a wireless power transmission apparatus 1, utilizing the above described characteristic enables adjustment of the input impedance Zin in a wireless power transmission apparatus 1 thereby enabling control of the power output from the wireless power transmission apparatus 1, simply by physically varying the distance d34 between the power-receiving resonator 32 and the power-receiving coil 31.
It should be noted that a case of varying the distance d12 between the power-supplying coil 21 and the power-supplying resonator 22 and the distance d34 between the power-receiving resonator 32 and the power-receiving coil 31 was described above as an example method for adjusting the coupling coefficients k12, k23, and k34 which are parameters for controlling the input impedance Zin in the wireless power transmission apparatus 1. The method of adjusting the coupling coefficients k12, k23, and k34 is not limited to this. For example, the following approaches are possible: disposing the power-supplying resonator 22 and the power-receiving resonator 32 so their axes do not match with each other; giving an angle to the coil surfaces of the power-supplying resonator 22 and the power-receiving resonator 32; varying the property of each element (resistor, capacitor, coil) of the power-supplying coil 21, the power-supplying resonator 22, the power-receiving resonator 32, and the power-receiving coil 31; varying the driving frequency of the AC power supplied to a power-supplying module 2.
Next, the following describes with reference to
The wireless power transmission apparatus 1 to be designed in the design method is implemented on an RF headset 200 and a charger 201 shown in
First, as shown in
Next, the distance between the power-supplying module 2 and the power-receiving module 3 is determined (S2). The distance is the distance d23 between the power-supplying resonator 22 and the power-receiving resonator 32, while the RF headset 200 having therein the power-receiving module 3 is placed on the charger 201 having therein the power-supplying module 2, i.e., during the charging state. To be more specific, the distance d23 between the power-supplying resonator 22 and the power-receiving resonator is determined, taking into account the shapes and the structures of the RF headset 200 and the charger 201.
Further, based on the shape and the structure of the RF headset 200, the coil diameters of the power-receiving coil 31 in the power-receiving module 3 and the coil of the power-receiving resonator 32 are determined (S3).
Further, based on the shape and the structure of the charger 201, the coil diameters of the power-supplying coil 21 in the power-supplying module 2 and the coil of the power-supplying resonator 22 are determined (S4).
Through the steps of S2 to S4, the coupling coefficient K23 between the power-supplying resonator 22 (coil L2) of the wireless power transmission apparatus 1 and the power-receiving resonator 32 (coil L3), and the power transmission efficiency of the wireless power transmission apparatus 1 are determined.
Based on the power reception amount in the power-receiving module 3 determined in S1 and on the power transmission efficiency determined through S2 to S4, the minimum power supply amount required for the power-supplying module 2 is determined (S5).
Then, the design values of the input impedance Zin in the wireless power transmission apparatus 1 is determined, taking into account the power reception amount in the power-receiving module 3, the power transmission efficiency, and the minimum power supply amount required to the power-supplying module 2 (S6).
Then, the distance d12 between the power-supplying coil 21 and the power-supplying resonator 22 and the distance d34 between the power-receiving resonator 32 and the power-receiving coil 31 are determined so as to achieve the design value of the input impedance Zin determined in S6 (S7). Specifically, to determine the distance d12 between the power-supplying coil 21 and the power-supplying resonator 22 and the distance d34 between the power-receiving resonator 32 and the power-receiving coil 31 are determined so as to achieve the input impedance Zin determined in S6, an adjustment is conducted based on the characteristic that the value of the input impedance Zin of the wireless power transmission apparatus 1 increases, by reducing the distance d12 between the power-supplying coil 21 and the power-supplying resonator 22 when the distance d23 between the power-supplying resonator 22 and the power-receiving resonator 32 and the distance d34 between the power-receiving resonator 32 and the power-receiving coil 31 are fixed, or the characteristic that the value of the input impedance Zin of the wireless power transmission apparatus 1 decreases by reducing the distance d34 between the power-receiving resonator 32 and the power-receiving coil 31 when the distance d12 between the power-supplying coil 21 and the power-supplying resonator 22 and the distance d23 between the power-supplying resonator 22 and the power-receiving resonator 32 are fixed.
With the above-described manufacturing method of the wireless power transmission apparatus 1 including the above design method and the wireless power transmission apparatus 1 having undergone the above-described design process, there is provided a wireless power transmission apparatus 1 in which power to be supplied by means of wireless power transmission is adjustable by setting the value of the input impedance Zin in the wireless power transmission apparatus 1, without a need of an additional device. In other words, manufacturing of a wireless power transmission apparatus 1 capable of controlling power to be supplied is possible without a need of an additional component in the wireless power transmission apparatus 1.
Although the above description of the manufacturing method deals with an RF headset 200 as an example, the method is applicable to any devices having a rechargeable battery; e.g., tablet PCs, digital cameras, mobile phone phones, earphone-type music player, hearing aids, and sound collectors.
Although the above description deals with a wireless power transmission apparatus 1 configured to perform power transmission by means of magnetic coupling using a resonance phenomenon (magnetic field resonant state) between resonators (coils) provided to a power-supplying module 2 and a power-receiving module 3, the present invention is applicable to a wireless power transmission apparatus 1 configured to perform power transmission by using electromagnetic induction between coils.
Further, although the above description assumes the wireless power transmission apparatus 1 is mounted in a portable electronic device, the use of such an apparatus is not limited to small devices. For example, with a modification to the specifications according to the required power amount, the wireless power transmission apparatus 1 is mountable to a relatively large system such as a wireless charging system in an electronic vehicle (EV), or to an even smaller device such as a wireless endoscope for medical use.
Although the above descriptions have been provided with regard to the characteristic parts so as to understand the present invention more easily, the invention is not limited to the embodiments and the examples as described above and can be applied to the other embodiments and examples, and the applicable scope should be construed as broadly as possible. Furthermore, the terms and phraseology used in the specification have been used to correctly illustrate the present invention, not to limit it. In addition, it will be understood by those skilled in the art that the other structures, systems, methods and the like included in the spirit of the present invention can be easily derived from the spirit of the invention described in the specification. Accordingly, it should be considered that the present invention covers equivalent structures thereof without departing from the spirit and scope of the invention as defined in the following claims. In addition, it is required to sufficiently refer to the documents that have been already disclosed, so as to fully understand the objects and effects of the present invention.
| Number | Date | Country | Kind |
|---|---|---|---|
| 2013-039797 | Feb 2013 | JP | national |
| Filing Document | Filing Date | Country | Kind |
|---|---|---|---|
| PCT/JP2013/077436 | 10/9/2013 | WO | 00 |
