Patent Grant
9972900
The present invention relates to a distributor and a planar antenna, and more specifically, to improvement of a distributor that is connected with an input line and two or more output lines respectively formed on a dielectric substrate as microstrip lines, and distributes high frequency power fed from a feeding point to a branching point through the input line to the two or more output lines.
A microstrip antenna is a planar antenna in which a feed line extending with a substantially constant width and radiating elements excited by a traveling wave propagating through the feed line are formed on a dielectric substrate, and fed with power using a waveguide or the like. The feed line is a microstrip line configured to include a microstrip conductor formed on the front surface of the dielectric substrate and a grounding plate formed on the back surface of the dielectric substrate. Such a planar antenna uses a distributor in order to distribute high frequency power according to the number of radiating elements. The distributor is a power distributing circuit adapted to distribute the high frequency power fed from a feeding point to a branching point through an input line to two or more output lines (see, for example, Patent Literatures 1 and 2).
Patent Literature 1: Japanese Unexamined Patent Publication JP-H11-330811-A
Patent Literature 2: Japanese Unexamined Patent Publication JP-2001-196816-A
A conventional distributor has the problem of having a large reflection amount and large insertion loss. Also, providing an impedance transformer to reduce a reflection amount gives rise to the problem of changing a ratio in power distribution among output lines.
A ratio in power distribution among the output lines Lo1 to Lo3 is determined by the characteristic impedances of the output lines Lo1 to Lo3. Also, the characteristic impedance of a feed line is determined by the width of the line, dielectric constant of the dielectric substrate, thickness of the dielectric substrate, and the like. For this reason, changing the widths of the output lines Lo1 to Lo3 can adjust the ratio in power distribution among the output lines Lo1 to Lo3. However, the distributor 100 illustrated had a large reflection amount and large insertion loss.
On the other hand, in the case of the distributor 110, the reflection amount is 0.09, which is very small. However, the transmission amounts of the output lines Lo1 and Lo3 are 0.81, and as compared with the distributor 100 not including the impedance transformer 111, it turns out that a ratio in power distribution is small. As described, the change in power distribution ratio among the output lines Lo1 to Lo3 prevents high frequency power from being appropriately distributed to respective radiating elements, and consequently, desired directivity cannot be obtained.
The present invention is made in consideration of the above situations, and intends to provide a distributor capable of reducing insertion loss while suppressing a ratio in power distribution among output lines from being changed. In particular, the present invention intends to provide a distributor capable of reducing insertion loss while suppressing a ratio in power distribution from being changed from a value corresponding to the line widths of output lines.
Also, the present invention intends to provide a planar antenna capable of obtaining desired directivity while reducing the insertion loss of a distributor.
A distributor according to a first aspect of the present invention is a distributor that is connected with an input line and two or more output lines respectively formed on a dielectric substrate as microstrip lines, and distributes to said two or more output lines high frequency power fed from a feeding point to a branching point through the input line. In addition, the distributor includes a stub area that is formed in the input line, is separated from the branching point, and has a rectangular shape wider than line widths of the input line on a feeding point side and on a branching point side. Further, the stub area is configured to be arranged in a position where the distance between an edge on the feeding point side and lateral edges on an input side of the output lines substantially perpendicular to the input line is substantially equal to (λg/4)×(2n+1) where λg is a guide wavelength and n is an integer.
In such a configuration, since the difference in propagation path is an odd multiple of the half wavelength, after propagation through the input line, a reflected wave reflected at a position corresponding to the edge of the stub area on the feeding point side, and a reflected wave reflected at a position corresponding to the lateral edges on the input side of the output lines substantially perpendicular to the input line are mutually cancelled out by interference. For this reason, a reflection amount when the high frequency power is fed to the branching point through the input line can be reduced to reduce the insertion loss of the distributor. Also, by separating the stub area from the branching point, an area narrower in line width than the stub area is formed between the stub area and the branching point, and therefore the electromagnetic coupling between the stub area and the output lines can be weakened. For this reason, a ratio in power distribution can be suppressed from being changed from a value corresponding to the line widths of the output lines.
A distributor according to a second aspect of the present invention is, in addition to the above configuration, configured such that the length of the stub area in a line length direction is substantially equal to (λg/4)×(2m+1) where m is an integer. In such a configuration, since the difference in propagation path is an odd multiple of the half wavelength, after propagation through the input line, a reflected wave reflected at the position corresponding to the edge of the stub area on the feeding point side, and a reflected wave reflected at a position corresponding to an edge of the stub area on the side opposite to the feeding point, i.e., an edge on the branching point side are mutually cancelled out by interference. For this reason, the reflection amount when the high frequency power is fed to the branching point through the input line can be further reduced.
A distributor according to a third aspect of the present invention is, in addition to the above configuration, configured such that the line widths of the input line on the branching point side rather than the stub area and on the feeding point side rather than the stub area are substantially equal to each other. In such a configuration, since the line width of the input line is the same as that in the case where the stub area is not provided, a ratio in power distribution between the output lines corresponding to that in the case where the stub area is not provided can be achieved.
A distributor according to a fourth aspect of the present invention is, in addition to the above configuration, configured such that the stub area includes two protrusion parts that protrude from both lateral edges of the input line in mutually opposite directions. In the case of a distributor of which an input line and two output lines substantially perpendicular to the input line are connected to each other at a branching point, the configuration according to the fourth aspect makes it possible to uniformly distribute high frequency power to the output lines.
A distributor according to a fifth aspect of the present invention is, in addition to the above configuration, configured such that the branching point is formed as a cross-shaped area connected with the input line, two of the output lines substantially perpendicular to the input line, and one output line substantially parallel to the input line. Such a configuration makes it possible to reduce a reflection amount at the branching point while suppressing a ratio in power distribution between the two output lines substantially perpendicular to the input line from being changed.
A planar antenna according to a sixth aspect of the present invention includes: feed lines that are formed on a dielectric substrate as microstrip lines; a distributor that is connected with an input line and two or more output lines respectively as the feed lines, and distributes high frequency power fed from a feeding point to a branching point through the input line to the two or more output lines; and two or more radiating elements that are excited by traveling waves propagating through the output lines. In addition, the distributor has a stub area that is formed in the input line, is separated from the branching point, and has a rectangular shape wider than line widths of said input line on a feeding point side and on a branching point side. Further, the stub area is configured to be arranged in a position where the distance between an edge on the feeding point side and lateral edges on an input side of the output lines substantially perpendicular to the input line is substantially equal to (λg/4)×(2n+1) where λg is a guide wavelength and n is an integer.
In such a configuration, since the difference in propagation path is an odd multiple of the half wavelength, after propagation through the input line, a reflected wave reflected at a position corresponding to the edge of the stub area on the feeding point side, and a reflected wave reflected at a position corresponding to the lateral edges on the input side of the output lines substantially perpendicular to the input line are mutually cancelled out by interference. For this reason, a reflection amount when the high frequency power is fed to the branching point of the distributor through the input line can be reduced to reduce the insertion loss of the distributor. Also, by separating the stub area from the branching point, an area narrower in line width than the stub area is formed between the stub area and the branching point, and therefore the electromagnetic coupling between the stub area and the output lines can be weakened. For this reason, a ratio in power distribution can be suppressed from being changed from a value corresponding to the line widths of the output lines. As a result, the planar antenna is capable of obtaining desired directivity because the high frequency power is appropriately distributed to the respective output lines by the distributor and supplied to the respective radiating element.
The present invention can provide a distributor capable of reduce insertion loss while suppressing a ratio in power distribution among output lines from being changed. In particular, the present invention can provide a distributor capable of reducing insertion loss while suppressing a ratio in power distribution from being changed from a value corresponding to the line widths of output lines.
Also, the planar antenna according to the present invention is capable of obtaining desired directivity while reducing the insertion loss of a distributor.
In the following description, the top, bottom, left, and right refer to those with each of the drawing sheets as a reference.
<Planar Antenna 1>
The dielectric substrate 10 is an antenna substrate made of a dielectric. As the dielectric substrate 10, for example, a rectangular-shaped printed substrate made of a fluorine resin or an insulating resin is used. Each of the feed lines 3 is a transmission line through which a traveling wave propagates, and formed as a microstrip line extending with a substantially constant width along the front surface of the dielectric substrate 10.
Each of the feed lines 3 is configured to include the dielectric substrate 10, a microstrip conductor formed on the front surface of the dielectric substrate 10, and a grounding plate (not illustrated) formed on the back surface of the dielectric substrate 10. The grounding plate is formed as a conductor pattern adapted to function as a ground electrode for the feed lines 3 and the distributor 4, and almost covers the entire back surface of the dielectric substrate 10.
The converter 2 is a power conversion circuit that converts the high frequency power between the waveguide and the feed line 3, and configured to include an opening part 21 formed in the grounding plate, a matching element 22 formed inside the opening part 21, and a shorting plate 23 formed on the front surface of the dielectric substrate 10. The waveguide is fixed to the planar antenna 1 with an end surface thereof being in contact with the grounding plate.
The opening part 21 forms a rectangular-shaped closing area that closes the waveguide, and has dimensions corresponding to wide walls and narrow walls of the waveguide. For example, the opening part 21 is a laterally-long rectangular-shaped through-hole penetrating through the grounding plate, and arranged with the long sides corresponding to the wide walls of the waveguide and the short sides corresponding to the narrow walls. The matching element 22 is a resonator adapted to resonate the electromagnetic wave, and has a rectangular-shaped conductor pattern formed in an island shape inside the opening part 21.
The shorting plate 23 has a rectangular-shaped conductor pattern for shorting the waveguide, and covers the opening part 21 as well as being formed with a cutout 23a for arranging the feed line 3. The cutout 23a is formed in the central part of the opening part 21 in the horizontal direction, in which the top end part of the feed line 3 extending in the vertical direction is arranged. The top end part of the feed line 3 crosses the long edge of the opening part 21 and the bottom edge of the matching element 22. In the planar antenna 1, the high frequency power is fed to the feed line 3 from the converter 2 as a feeding point.
The distributor 4 is a power distributing circuit that is connected with an input line Lin and output lines Lo1 to Lo3, and distributes the high frequency power fed from the feeding point to a branching point 41 through the input line Lin to the two or more output lines Lo1 to Lo3. The distributor 4 is a three-branching type distributing circuit that distributes the high frequency power to the three output lines Lo1 to Lo3, and has the branching point 41 connected with the input line Lin and the output lines Lo1 to Lo3, and a stub area 42 wider in line width than the input line Lin.
All of the input line Lin and the output lines Lo1 to Lo3 are the feed lines 3 formed on the dielectric substrate 10 as the microstrip lines. The input line Lin linearly extends from the branching point 41 toward the top, and the top end part thereof is arranged in the cutout 23a of the shorting plate 23. The output line Lo1 linearly extends from the branching point 41 toward the left. The output line Lo1 bends on the way, and connects to the feed line 3 extending toward the bottom.
The output line Lot linearly extends from the branching point 41 toward the bottom. The output line Lo3 linearly extends from the branching point 41 toward the right. The output line Lo3 bends on the way, and connects to the feed line 3 extending toward the bottom. The stub area 42 functions as a reflection suppressing element adapted to suppress reflection at the branching point 41, and is provided in the input line Lin.
Each of the radiating elements 5 is an antenna element that is excited by a traveling wave propagating through a corresponding feed line 3 to radiate an electromagnetic wave to free space, and has a shape extending in a direction intersecting with the feed line 3. The radiating element 5 is connected to the feed line 3 at one end, and opened at the other end. The element length of the radiating element 5 is substantially half a guide wavelength λg. The guide wavelength λg is a wavelength of the electromagnetic wave propagating through the feed line 3.
In the planar antenna 1, the two or more radiating elements 5 are formed along the feed lines 3, and each of the radiating elements 5 has a rectangular-shaped conductor pattern. The number and shapes of the radiating elements 5 are determined depending on performance and directional characteristics required for the planar antenna 1. Each of the matching elements 6 is a termination circuit adapted to terminate a corresponding feed line 3, and has a rectangular-shaped conductor pattern. The matching element 6 is arranged at the bottom end of the feed line 3.
Along the output line Lo2, six radiating elements 5 are arranged, and along each of the output lines Lo1 and Lo3, four radiating elements 5 are arranged. These radiating elements 5 are arranged so as to radiate to free space the electromagnetic waves respectively having the same phases and uniform polarization planes, all of which tilt with respect to the lateral edges of the feed lines 3. Also, the radiating elements 5 are provided along both lateral edges of the corresponding feed lines 3.
Radiating elements 5 formed along the right lateral edge of each of feed lines 3 are arranged at predetermined intervals so as to be excited at mutually the same phase. For example, the respective radiating elements 5 are arranged at intervals equal to an integral multiple of the guide wavelength λg. Also, these radiating elements 5 are arranged parallel to each other to make the polarization planes uniform. Further, in order to make it possible to obtain desired directivity, the element widths of the respective radiating elements 5 are made different. For example, the element width of a radiating element 5 increases with increasing distance from the feeding point. Radiating elements 5 formed along the left lateral edge of the feed line 3 are also configured to be similar to the radiating elements 5 formed along the right lateral edge of the feed line 3.
The conductor patterns included in the converter 2, feed lines 3, distributor 4, radiating elements 5, and matching elements 6 are fabricated by attaching a metal thin film, e.g., copper foil, on the dielectric substrate 10 and patterning the metal thin film on the dielectric substrate 10 by etching or the like. The line widths of the feed lines 3 are determined depending on a frequency, bandwidth, and radiation characteristics of an electromagnetic wave to be transceived. Also, the line widths of the feed lines 3 are shorter than the guide wavelength λg.
<Distributor 4>
The distributor 4 is configured to include the branching point 41 formed as a cross-shaped area and the rectangular-shaped stub area 42. The stub area 42 is formed in the input line Lin, separated from the branching point 41, and of a convex shape formed by expanding the line width of the input line Lin left and right. Note that a part of the input line Lin on the feeding point side rather than the stub area 42 is referred to as a first area La, and a part on the branching point side rather than the stub area 42 is referred to as a second area Lb.
The stub area 42 is a rectangular-shaped area of which the line width Ws is wider than the line width of the first area La and the line width of the second area Lb. Accordingly, the second area Lb is narrower in line width than the stub area 42, and functions as a coupling buffer area adapted to weaken the electromagnetic coupling between the stub area 42 and the output lines Lo1 and Lo3.
In the case of the distributor 4 illustrated in
The stub area 42 corresponds to an open stub because the fore ends of the protrusion parts are open ends. The stub area 42 is arranged in a position where the distance d1 between the input edge 42a of the stub area 42 and the lateral edges 3a on an input side of the output lines Lo1 and Lo3 is substantially equal to (λg/4)×(2n+1) where λg is the guide wavelength and n is an integer. The input edge 42a is an edge on the feeding point side between the two edges of the stub area 42 extending in the horizontal direction. The term “substantially equal” means that the difference between the distance d1 and (λg/4)×(2n+1) is sufficiently small as compared with the guide wavelength λg. For example, the difference is λg/8 or less.
In such a configuration, since the difference 2d1 in propagation path is an odd multiple of the half wavelength (λg/2), after propagation through the input line Lin, a reflected wave reflected at a position corresponding to the input edge 42a of the stub area 42, and a reflected wave reflected at a position corresponding to the lateral edges 3a on the input side of the output lines Lo1 and Lo3 are mutually cancelled out by interference. For this reason, a reflection amount when the high frequency power is fed to the branching point 41 through the input line Lin can be reduced to reduce the insertion loss of the distributor 4. It can be understood that this is because input impedance as seen from the feeding point side is matched between the position corresponding to the input edge 42a of the stub area 42 and the position corresponding to the lateral edges 3a on the input side of the output lines Lo1 and Lo3 at the branching point 41.
Also, by separating the stub area 42 from the branching point 41, the first area Lb narrower in line width than the stub area 42 is formed between the branching point 41 and the stub area 42, and therefore the electromagnetic coupling between the stub area 42 and the output lines Lo1 and Lo3 can be weakened. For this reason, a ratio in power distribution can be suppressed from being changed from a value corresponding to the line widths of the output lines Lo1 and Lo3.
The stub area 42 has a stub length Ls substantially equal to (λg/4)×(2m+1) where m is an integer. The stub length Ls is length in a line length direction, i.e., in the vertical direction, and given that between the two edges of the stub area 42 extending in the horizontal direction, an edge on an edge opposite to the feeding point i.e., an edge on the branching point side is referred to as an output edge 42b, corresponds to the distance between the input edge 42a and the output edge 42b. Both of the input edge 42a and the output edge 42b are edges substantially perpendicular to the lateral edges 3a of the input line Lin. For example, the distributor 4 has a conductor pattern having d1=λg/4)×3, Ls=(λg/4), and d2=(λg/2).
In such a configuration, since the difference 2 Ls in propagation path is an odd multiple of the half wavelength (λg/2), after propagation through the input line Lin, a reflected wave reflected at the position corresponding to the input edge 42a of the stub area 42, and a reflected wave reflected at a position corresponding to the output edge 42n of the stub area 42 are mutually cancelled out by interference. For this reason, the reflection amount when the high frequency power is fed to the branching point 41 through the input line Lin can be further reduced.
Note that the distance d2 between the output side 42b and the lateral edges 3a on the input side of the output lines Lo1 and Lo3 is d2=(d1−Ls). For this reason, in the case where the distance d1 is d1=(λg/4)×(2n+1) and the stub length Ls is Ls=(λg/4)×(2m+1), the distance d2 is an integral multiple of the half wavelength (λg/2).
The line width Ws of the stub area 42 is determined by the characteristic impedances of the input line Lin and the output lines Lo1 to Lo3. For example, the line width Ws has length corresponding to the geometric mean between the characteristic impedance of the input line Lin and the combined impedance of the branching point 41. Also, the line width of the second area Lb is substantially equal to that of the first area La. In such a configuration, since the line width of the input line Lin is the same as that in the case where the stub area 42 is not provided, a ratio in power distribution between the output lines Lo1 and Lo3 corresponding to that in the case where the stub area 42 is not provided can be achieved.
When comparing the operation characteristics of this distributor 4 with the operation characteristics of the distributor 110 including the impedance transformer 111, it turns out that the distributor 4 can suppress reflection to the same degree as the distributor 110. On the other hand, the transmission amounts of the output lines Lo1 and Lo3 are 0.88, from which it turns out that a ratio in power distribution corresponding to that of the distributor 100 not including the impedance transformer 111 is achieved.
In the case of the distributor 4 illustrated in
That is, by making the protrusion length of the stub area 42 different between the left and the right, the ratio in power distribution between the output lines Lo1 and Lo3 can be adjusted. For example, by increasing the protrusion length on the output line Lo3 side (right side), a power distribution ratio of the output line Lo1 can be made larger than that of the output line Lo3.
In this analysis result, the reflection amount takes local minimum values of −26.6 dB at Ls=0.14, −20.8 dB at Ls=0.64 and −17.8 dB at Ls=1.20, whereas the reflection amount is −7.1 dB at the stub length Ls=0, i.e., in the case where the stub area 42 is not provided. That is, when the stub length Ls reaches a predetermined value shorter than λg/4, the reflection amount takes the minimum first, and as the stub length Ls is increased, a minimum appears at repetition intervals of approximately λg/2.
In this analysis result, the reflection amount takes minimum values of −29.4 dB, −26.9 dB, and −23.5 dB at Ls=0.14, 0.64, and 1.13, whereas the reflection amount is −7.1 dB at the stub length Ls=0. That is, when the stub length Ls reaches a predetermined value shorter than λg/4, the reflection amount takes the minimum first, and as the stub length Ls is increased, a minimum appears at repetition intervals of approximately λg/2.
When fixing the output edge 42b at a position where the distance d2 from the lateral edges 3a on the input line side of the output lines Lo1 and Lo3 is (λg/2)×(2k+1) (where k is an integer equal to or more than 1) as well, reflection characteristics similar to those when the output side 42b was fixed at the position corresponding to (λg/2) can be obtained.
In this analysis result, the reflection amount takes minimum values of −8.1 dB, −8.6 dB, and −9.2 dB at Ls=0.49, 0.99, and 1.48, respectively, whereas the reflection amount is −7.1 dB at the stub length Ls=0. However, it turns out that these minimum values are larger than a target reflection amount, for example, −15 dB; at any point other than the minimum points, the reflection amount is larger than that in the case where the stub area 42 and the second area LB is provided; and the stub length Ls enabling matching is not present.
The reason for such reflection characteristics may be because input impedance as seen from the feeding point side is the same between the position corresponding to the input edge 42a of the stub area 42 and the position corresponding to the lateral edges 3a on the input side of the output lines Lo1 and Lo3 at the branching point 41 (the both positions have the positional relationship where the reflected waves are combined at the same phase), and therefore cannot be matched even when changing the stub length Ls.
From the analysis results of the reflection characteristics illustrated in
Branching points 41 are formed as cross-shaped areas, respectively. The line width Ws of a stub area 42 of the distributor 4 in
According to the present embodiment, the reflection amount when the high frequency power is fed to the branching point 41 through the input line Lin can be reduced to reduce the insertion loss of the distributor 4. In particular, the reflection amount at the branching point 41 can be reduced while suppressing the ratio in power distribution between the two output lines Lo1 and Lo3 substantially perpendicular to the input line Lin from being changed. Also, by separating the stub area 42 from the branching point 41, the second area Lb narrower in line width than the stub area 42 is formed between the stub area 42 and the branching point 41, and therefore the electromagnetic coupling between the stub area 42 and the output lines Lo1 to Lo3 can be weakened.
Note that in the present embodiment, an example of the case where the line width of the second area Lb is substantially equal to that of the first area La is described. However, the present invention does not limit the line width of the second area Lb to this. For example, the line width of the second area Lb may be wider or narrower than the line width of the first area La as long as being narrower than the line width Ws of the stub area 42.
Also, in the present embodiment, an example of the case where the stub area 42 is arranged in the position where the distance d1 is substantially equal to (λg/4)×(2n+1), and the stub length Ls is substantially equal to (λg/4)×(2m+1) is described. However, the present invention does not limit the configuration of the stub area 42 to this. For example, as long as being arranged in the position where the distance d1 is substantially equal to (λg/4)×(2n+1), the stub area 42 may be configured such that the stub length Ls is not equal to (λg/4)×(2m+1). Also, as long as d1>Ls is met, the second area Lb of the input line Lin is present, and therefore a distributor in which the stub area 42 is arranged in a position where the distance d1 is substantially equal to (λg/4), and the stub length Ls is substantially equal to (λg/4) is also included in the present invention.
| Number | Date | Country | Kind |
|---|---|---|---|
| 2014-188244 | Sep 2014 | JP | national |
| Number | Name | Date | Kind |
|---|---|---|---|
| 20080117004 | Mochizuki | May 2008 | A1 |
| 20130027259 | Fujita | Jan 2013 | A1 |
| Number | Date | Country |
|---|---|---|
| H11-330811 | Nov 1999 | JP |
| 2001196816 | Jul 2001 | JP |
| Number | Date | Country | |
|---|---|---|---|
| 20160079674 A1 | Mar 2016 | US |
