Electrically programmable three-dimensional memory-based self test

Abstract

The electrically programmable three-dimensional memory (EP-3DM) can be used to carry the test data and/or test-data seeds for the circuit-under-test (CUT). When integrated with the CUT, EP-3DM has minimum impact to the layout of the CUT. Apparently, CUT with integrated EP-3DM supports IC self-test. Moreover, with a large bandwidth with the CUT, EP-3DM-based IC self-test enables at-speed test.

Description

BACKGROUND

1. Technical Field of the Invention

The present invention relates to the field of integrated circuits, and more particularly to electrically programmable three-dimensional (3-D) memory-based IC self-test.

2. Related Arts

In a three-dimensional (3-D) integrated circuit (3D-IC), one or more 3D-IC layers are stacked one above another on top of a substrate. Each IC layer comprises functional blocks such as logic, memory and analog blocks. It is typically comprised of non-single-crystalline (poly, microcrystalline or amorphous) semiconductor material. Because logic and analog blocks are sensitive to defects and non-single-crystalline semiconductor material has a large defect density, the 3D-IC comprising logic and/or analog blocks have a low yield. Moreover, logic and/or analog blocks consume large power. The three-dimension integration of these blocks faces many heat-dissipation issues. On the other hand, a memory block is less sensitive to defects because the defect-induced errors can be corrected (by, for example, redundancy circuit). Moreover, it consumes little power. Accordingly, memory is better suited for the 3-D integration.

In a three-dimensional memory (3D-M), one or more memory levels are stacked one above another on top of a substrate. As illustrated in FIG. 1 , the two physical memory levels 100 , 200 of the 3D-M 0 are stacked one by one on a substrate 0 s . On each memory level 100 , there are a plurality of address-select lines (including word line 20 a and bit line 30 a ) and 3D-M cells ( 1 aa . . . ). Substrate 0 s comprises a plurality of transistors. Contact vias ( 20 av , 30 av . . . ) provide electrical connection between address-select lines ( 20 a , 30 a . . . ) and the substrate circuit.

The 3D-M can be categorized through the means employed to alter its contents. If the contents can be altered using electrical means, this 3D-M is an electrically programmable 3D-M (EP-3DM); if the contents are altered using non-electrical means, then this 3D-M is a non-electrically programmable 3D-M (NEP-3DM).

The electrically programmable 3D-M (EP-3DM) can be further categorized into 3-D RAM (3D-RAM), 3-D write-once memory (a.k.a. 3-D one-time programmable, i.e. 3D-OTP), and 3-D write-many (3D-WM). The 3D-RAM cell is similar to a conventional RAM cell except that the transistors used therein are thin-film transistors (TFT) 1 t (FIG. 1 B). The 3D-OTP cell may comprise a 3D-ROM layer 22 (e.g. a diode layer) and an antifuse layer 22 a (FIG. 1 C). The integrity of the antifuse layer 22 a indicates the logic state of the 3D-OTP cell. The 3D-WM includes 3D-flash, 3D-MRAM (3-D magneto-resistive-material-based RAM), 3D-FRAM (3-D Ferroelectric-material-based RAM), 3D-OUM (3-D Ovonyx-unified-memory), etc. It may comprise active devices such as TFT 1 t (FIGS. 1 DA- 1 DB). The TFT-based 3D-WM may comprise a floating gate 30 fg (FIG. 1 DA) or a vertical channel 25 c (FIG. 1 DB).

An exemplary non-electrically programmable 3D-M (NEP-3DM) is mask-programmable 3-D read-only memory (3D-MPROM). It represents logic “1” with the existence of an info-via 24 (i.e. absence of dielectric 26 ) (FIG. 1 EA); and logic “0” with the absence of an info-via (i.e. existence of dielectric 26 ) (FIG. 1 EB). Similar to 3D-OTP cell (FIG. 1 C), it also comprises a 3D-ROM layer 22 (e.g. a diode layer).

3D-M can also be categorized as conventional semiconductor memory, i.e. it can be categorized into 3D-RAM and 3D-ROM (including 3D-MPROM, 3D-OTP, 3D-WM). This is the approach used by prior patents and patent applications filed by the same inventor (U.S. Pat. No. 5,835,396, U.S. patent application Ser. No. 10/230,648, etc.) In this application, both categorizations are used interchangeably.

With low-cost, high density and large bandwidth, the 3D-M has a strong competitive edge. However, because it is typically based on non-single-crystalline semiconductor, the performance of the 3D-M cell cannot yet compete with the conventional memory. For the 3D-M designed and manufactured in conventional approaches, its performance, such as read-write speed, unit-array capacity, intrinsic yield and programmability, needs further improvement.

The present invention provides an improved three-dimensional memory (3D-M). It has better integratibility, speed, density/cost and programmability. The 3D-M can be used to form three-dimensional integrated memory (3DiM), e.g. computer-on-a-chip (ConC) and player-on-a-chip (PonC). ConC/PonC offers excellent data security. Another 3D-M application of great importance is in the area of the integrated-circuit (IC) testing. 3D-M carrying the IC test data can be integrated with the circuit-under-test (CUT), thus enabling at-speed test and self-test.

It should be noted that, although various types of the 3D-M (including both EP-3DM- and NEP-3DM) are described hereinafter, the scope of this Application is limited to the EP-3DM only. The NEP-3DM is expressly excluded from the scope of this Application.

OBJECTS AND ADVANTAGES

It is a principle object of the present invention to provide an integrated circuit (IC) with self-test and at-speed test capabilities.

It is a further object of the present invention to provide an IC self-test based on electrically programmable three-dimensional memory (EP-3DM).

It is a further object of the present invention to provide an IC self-test method with minimum impact to the layout of the circuit-under-test.

In accordance with these and other objects of the present invention, an EP-3DM-based IC self-test is disclosed.

SUMMARY OF THE INVENTION

Compared with conventional memory, one greatest advantage of the 3D-M is its integratibility. Because its memory cells do not occupy substrate, most substrate real estate can be used to build complex substrate integrated circuits (substrate-IC). The substrate-IC may comprise conventional memory block, processing unit, analog block and others. 3D-M SoC (system-on-a-chip) formed from the integration between the 3D-M and substrate-IC is referred in the present invention as three-dimensional integrated memory (3DiM). The 3DiM can further improve the data security, speed, yield and software upgradibility of the 3D-M.

In a 3DiM, the substrate-IC may comprise an embedded read-write memory (eRWM) and/or an embedded processor (eP). The performance of the 3D-M and the eRWM are complementary to each other: 3D-M excels in integratibility and density/cost; RWM is better in speed and programmability. The integration of the 3D-M and the RWM combines their individual strength and can achieve an optimized system performance. On the other hand, the integration of the 3D-M and the eP can enable the on-chip processing of the 3D-M data (data stored in the 3D-M), thus improving the 3D-M data security.

One exemplary eRWM is embedded RAM (eRAM). The eRAM has a small latency. It can be used as a cache for the 3D-M data, i.e. it keeps a copy of the 3D-M data. When the eP seeks data, it searches first in the eRAM. If not found, it will then search the 3D-M. This approach reconciles the speed difference between the eP and the 3D-M. Another exemplary eRWM is embedded ROM (eROM). In general, eROM comprises non-volatile memory (NVM). The excellent programmability of the eROM can remedy the limited programmability of the 3D-M. Accordingly, the eROM is an ideal storage device for the correctional data (data used to correct defect-induced errors) and upgrade code of the 3D-M.

Computer-on-a-chip (ConC) is realized by integrating a 3D-M with an eP and an eRWM. It can perform many task of a today's computer. One exemplary ConC is player-on-a-chip (PonC). PonC can store and play contents, including audio/video (A/V) materials, electronic books, electronic maps and others. It provides excellent copyright protection to these contents. For the conventional content-storage technologies such as optical discs, pirates can easily steal the original contents by monitoring the output signal from the content carrier (i.e. the medium that carries the content, including optical discs ROM chips and others) or by reverse-engineering the content carrier. In a PonC, the 3D-M is integrated with a content player (preferably with an on-chip D/A converter). Its output is analog (A/V) signal and/or decoded (A/V) signal. Accordingly, the original contents do not appear anywhere outside the PonC and therefore, cannot be digitally duplicated. Thus, excellent copyright protection can be achieved.

For a 3DiM using a mask-programmable 3D-M to store data (e.g. contents, codes), the data represented by the info-vias in the 3D-M are preferably encrypted. In addition, 3DiM preferably comprises an on-chip decryption engine. This on-chip decryption engine decrypts the 3D-M data. The decrypted data are directly sent to the other functional blocks on the 3DiM. For this type of the 3DiM, it is very difficult to reverse-engineer the chip using means such as de-layering.

The present invention provides means for improving the 3D-M integratibility, both from a structural perspective and from a design perspective. From a structural perspective, simple 3D-M cell is preferred. To be more specific, the diode-based 3D-ROM, particularly 3D-MPORM, is the first-choice candidate. Moreover, if the 3D-M process requires relatively high temperature, the interconnect system for the substrate circuit is preferably made of refractory conductors (e.g. refractory metal) and thermally-stable dielectrics (e.g. silicon oxide, silicon nitride). Furthermore, there are preferably a plurality of gaps between certain address-select lines in the 3D-M array. With their help, embedded wires can pass through the 3D-M array and provide interface for the substrate-IC. In addition, for the high-speed substrate-IC, a shielding layer is preferably formed between at least a portion of the 3D-M layer and the substrate circuit.

From a design perspective, unit array (i.e. the basic memory array in a chip) preferably has large capacity. This can minimize the number of unit arrays on a 3D-M chip and therefore, minimize the effect of the 3D-M's peripheral circuits on the layout of the substrate-IC. Moreover, simple 3D-M peripheral circuit is preferred. Simple peripheral circuit occupies less substrate real estate. Accordingly, the saved space can be used to accommodate more powerful substrate-IC. Since 3D-MPROM does not need programming circuitry, it is advantageous over 3D-EPROM in this aspect. For the “write-once” 3D-EPROM, since its programming capability is not used “very often”, the programming voltage can be directly fed into the chip, rather than being generated on-chip.

With outstanding manufacturability and integratibility, 3D-MPROM is a very promising 3D-M. The present invention provides several self-aligned 3D-MPROM. In a self-aligned 3D-MPROM, the 3D-ROM layer is self-aligned with the word and bit lines and its formation does not require any individual pattern-transfer step. The 3D-ROM layer may be pillar-shaped, with one dimension equal to the word-line width and the other dimension equal to the bit-line width; or be a natural junction, which is naturally formed at the cross-point between the word and bit lines. Furthermore, interleaved memory levels can be used to further increase memory density. In a 3D-M with interleaved memory levels, two adjacent memory levels share one address-select line. In general, 3D-MPROM can use an nF-opening mask to define the 3D-M data. On an nF-opening mask, the opening dimension is n times (preferably, n˜2) the minimum dimension supported by this technology. It has a much lower mask cost.

Compared with conventional memory, the 3D-M is typically slower. This issue can be addressed both from a design perspective and from a system perspective. From a design perspective, techniques such as sense amplifier (S/A), full-read mode and self-timing are preferably used. With an S/A, the bit-line voltage swing required to trigger a logic output is small (˜100 mV), thus it takes less time to charge up the bit line and the latency is shortened. In the full-read mode, all data on a single word line are read out at the same time and therefore, the bandwidth is improved. Self-timing ensures data-validity and saves power. For programmable 3D-M, parallel programming improves the write speed.

From a system perspective, 3DiM is preferably used to hide the 3D-M latency. The eRAM in the 3DiM works as a cache for the 3D-M. After read, the 3D-M data latched at the S/A are copied into the eRAM word-by-word. When an external circuit seeks data from the 3DiM, it reads from the eRAM first. If there is a hit, the data is read out from the eRAM; otherwise the data is read out from the 3D-M. Although the performance of a single 3D-M cell cannot yet compete with the conventional memory, collectively, its system performance can match that of the conventional memory, even excel.

To improve its integratibility, 3D-M preferably has a large unit-array capacity. This can be achieved in several approaches. First of all, since N BL (N BL is the number of bit lines in a unit array) is not constrained, a unit array can be designed into a rectangular shape, i.e. N BL >N WL (N WL is the number of word lines in a unit array). Secondly, since N WL is constrained by the rectification ratio γ of the 3D-ROM cell during read, γ preferably has a large value. One γ-enhancement technique uses a large read voltage V R . With the usage of S/A, the reverse and forward biases in γ is decoupled: the largest reverse bias is just around the threshold voltage V T of the S/A (˜100 mV); whereas, the forward bias is controlled by V R , which can be separately adjusted by design. In general, the forward bias (e.g. ˜3V) is far greater than the reverse bias (e.g. ˜0.3V). Apparently, γ can be improved by using larger V R . Another γ-enhancement technique uses polarized 3D-ROM cell. In a polarized cell, the base materials in its upper and lower layers are different, or, it has different interfaces with its top and bottom electrodes.

To improve yield, a seamless 3D-ROM cell is preferably used to lower the intrinsic defects in a 3D-ROM array. In a seamless 3D-ROM cell, all defect-sensitive layers (i.e. 3D-ROM layer and at least the portion of the bottom and top electrodes adjacent to it), are formed in a seamless way, i.e. there is no pattern-transfer step between the formations of these layers. Alternatively, error-correction schemes such as error-correction code (ECC) and redundancy circuits can be used to correct the defect-induced errors. For ECC, Hamming code is preferably incorporated in the 3D-M array. For redundancy circuits, the eROM therein preferably stores the addresses and correctional data for defects. Redundancy circuits can correct word-line errors, bit-line errors and single-bit errors. The correctional process can be carried out right after the column decoder (correction-during-read), or, in the eRAM (correction-after-read).

Besides correcting word-line errors, the word-line redundancy block provides software upgradibility for the 3D-M. In the area of software upgrade, the word-line redundancy block is also referred to as flexible-code block. Software upgrade can also use address-translation. For address-translation, the 3D-M and the eROM form a unified memory space: the 3D-M stores the original code and the eROM stores the upgrade code. The substrate-IC further comprises an address-translation block. It treats all input addresses as virtual address and translates them into the physical address for the unified memory space. If the data refer to the original code, the physical address points to the 3D-M; if the data refer to the upgrade code, the physical address points to the eROM.

Another 3D-M application of great importance is IC-testing. For the conventional testing methodology, it is difficult to achieve at-speed test and field self-test. Moreover, conventional testers are expensive. With the advent of 3D-M, particularly 3D-ROM, these issues can be addressed. The 3D-M carrying test data is preferably integrated with the circuit-under-test (CUT). During test, input test vector is first downloaded from the 3D-M to the CUT; then the output from the CUT is compared with the expected test vector. Accordingly, the CUT performance can be examined. This 3D-M-based self-test (3DMST) has many advantages: 1. With 3-D integration, the bandwidth between the CUT and the 3D-M is large. This large bandwidth can enable at-speed test to high-speed IC; 2. 3DMST can enable field self-test and self-diagnosis, thus improving the system reliability; 3. Being low-cost, the 3D-M adds little extra cost to the CUT; 4. The 3D-M has little impact to the CUT layout; 5. With a large capacity, the test data in the 3D-M can provide excellent fault coverage to the CUT.

Test vectors can be downloaded from the 3D-M to the CUT in a serial or parallel fashion. During serial downloading, test vectors are shifted one-by-one into the scan chain, during parallel downloading, test vectors are shifted into the scan chain in parallel. The integrated circuits with 3DMST capability (i.e. 3DMST-IC) can also support techniques such as parallel self-test, mixed-signal testing, and printed-circuit board (PCB) system self-test. Moreover, to reduce the amount of test data to be carried by the 3D-M, techniques such as test-data compression and composite test are preferably used. In a composite test, the 3DMST is combined with other testing techniques such as BIST and external scan test. Composite test further lowers the testing cost and improves the test reliability.

During the 3DMST, if the output test vector (OTV) mismatches the expected test vector (ETV), there are two possibilities: one is the CUT is defective; the other is the 3D-M is defective. The second scenario can cause undesired yield loss. To avoid it, methodologies such as 3DMST-with-confidence and/or secondary test are preferably followed. The 3DMST-with-confidence guarantees that the 3D-M is error-free: if there are defect-induced errors, they are corrected before the 3DMST. For the part that fails the 3DMST, a secondary test, i.e. an external scan test (EST), can be performed. Still failing the EST test, it will then be treated as a bad part. This testing methodology is also referred to as dual testing. To reduce the EST test time, the questionable test vectors (QTV, i.e. the test vectors corresponding to the mismatched OTV and ETV) are recorded during the 3DMST. Then the secondary test is only performed to the QTV.

BRIEF DESCRIPTION OF THE DRAWINGS

FIG. 1A is a perspective view of a preferred 3D-M; FIG. 1B illustrates a preferred 3D-RAM cell based on thin-film transistors; FIG. 1C illustrates a preferred 3D-OTP cell based on antifuse; FIGS. 1 DA- 1 DB illustrates two preferred 3D-WM cells based on thin-film transistors; FIGS. 1 EA- 1 EB illustrate preferred logic “1” and “0” 3D-MPROM cells.

FIGS. 2A-2C illustrate a preferred 3DiM and its substrate-IC.

FIGS. 3A-3D illustrate several preferred computers-on-a-chip (ConC).

FIGS. 4A-4B illustrate two preferred players-on-a-chip (PonC).

FIGS. 5 AA- 5 CB illustrate several preferred shielding layers in a 3DiM.

FIGS. 6 AA- 6 CB illustrate several preferred interfacing structures for a substrate-IC.

FIGS. 7 AA- 7 BC illustrate several preferred folded-back address-decoders and their routing levels.

FIGS. 8A-8B compare the relative placements of the 1F- and nF-opening patterns with respect to address-select lines during a preferred 3D-MPROM process.

FIGS. 9A-9C illustrate several preferred self-aligned, pillar-shaped 3D-MPROM's and their preferred process flows.

FIGS. 10 A- 10 ED illustrate several preferred self-aligned, natural-junction 3D-MPROM's and their preferred process flows.

FIGS. 11A-11B illustrate two preferred 3D-EPROM cells with metal/semiconductor address-select lines.

FIGS. 12 AA- 12 CB″ illustrate several preferred inverted-U links and their preferred process flows.

FIGS. 13A-13C illustrate the symbol, basic block diagram and detailed block diagram for a preferred 3D-ROM core.

FIGS. 14A-14G illustrate the design of several preferred circuit blocks in the preferred 3D-ROM core.

FIGS. 15 AA- 15 AD explain sources for the latency; FIGS. 15 BA- 15 CC explain reference bit line and provide several preferred reference bit lines; FIG. 15D illustrates a preferred implementation of data bit lines, dummy bit lines and timing bit lines in a 3D-ROM array.

FIG. 16 illustrates a preferred timing diagram of various signals in a 3D-ROM core.

FIGS. 17A-17G illustrate several preferred cached 3D-M's (3DcM) and preferred read flows.

FIGS. 18A-18B illustrate a preferred 3D-EPROM with parallel programming; FIG. 18C illustrates a preferred 3D-EPROM with external programming source(s).

FIGS. 19 AA- 19 G illustrates several preferred means for increasing the 3D-M unit-array capacity.

FIGS. 20 AA- 20 CB explain several 3D-M defect types.

FIGS. 21A-21B illustrate two preferred seamless 3D-ROM cells.

FIGS. 22 A- 22 E′ illustrate several preferred process flows for seamless 3D-ROM cells.

FIGS. 23A-23B illustrate two preferred quasi-seamless 3D-ROM cells.

FIG. 24 illustrates a preferred 3D-M ECC circuit.

FIGS. 25 A- 25 DC illustrate several preferred 3D-M redundancy circuits.

FIGS. 26A-26C illustrate several preferred 3D-M's with software upgradibility.

FIGS. 27A-27B explain a conventional IC-testing methodology.

FIGS. 28A-28C illustrate a preferred implementation of 3D-M-based self-test (3DMST).

FIGS. 29 AA- 29 BD illustrate several preferred test-data downloading means.

FIGS. 30A-30C illustrate preferred parallel self-test, mixed-signal testing, printed-circuit board (PCB) system self-test.

FIGS. 31 AA- 31 BB illustrate several preferred test-data reducing means.

FIG. 32 illustrates a preferred 3DMST-with-confidence.

FIGS. 33 A- 33 CB illustrate several preferred 3DMST-IC with dual-testing capacity.

For the reason of simplicity, in this disclosure, the figure number with a missing appendix refers to all figures with that appendix. For example, FIG. 17 refers to FIGS. 17A-17H ; and FIG. 17E refers to FIGS. 17 EA- 17 EC.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT

1. Three-Dimensional Integrated Memory (3DiM)

FIG. 2A is a cross-sectional view of a 3DiM. In a 3DiM, 3D-M array 0 A is integrated with substrate circuit 0 s . 3D-M array 0 A comprises one or more three-dimensional (3-D) memory level 100 . Each 3-D memory level 100 comprises a plurality of address-select lines ( 20 a , 30 i . . . ) and 3D-M cells ( 1 ai . . . ). The address-select lines comprise metallic material and/or doped semiconductor material. Transistors 0 T and their interconnects ( 0 Ia, 0 Ib . . . ) form substrate circuit 0 s . From a circuit perspective, substrate circuit 0 s comprises a substrate-IC 0 SC and address decoders 12 , 18 / 70 . These address decoders perform address decoding for the 3D-M array 0 A Contact vias ( 20 av . . . ) provides electrical connection between the address-select lines ( 20 a . . . ) and the substrate circuit 0 s (e.g. address decoder).

In certain applications, the address-select lines in the 3D-M prefer to comprise poly-crystalline semiconductor (referring to FIGS. 9 - 11 ). The standard process to form poly-silicon requires a high temperature step of >500° C. To avoid damage to the substrate circuit, its interconnect system 0 I (including metal wires and the insulating dielectric between them) is preferably made of refractory conductors (e.g. refractory metal, doped poly-silicon, silicides) and thermally-stable dielectrics (e.g. silicon oxide, silicon nitride). Here, tungsten (W) is a good candidate for refractory conductors. It is a mature technology and its resistivity is only 5.2 μW·cm. The W-based substrate-IC can meet the processing-power requirements for most 3DiM applications, particularly audio/video (A/V) players.

FIG. 2B is a block diagram of the substrate circuit 0 s on the 3DiM. Since the 3D-M cells do not occupy substrate real estate and the address decoders 12 , 18 / 70 occupy just a small portion thereof, most substrate real estate can be used to build substrate-IC 0 SC. As illustrated in FIG. 2C , the substrate-IC 0 SC may comprise embedded RWM (eRWM) 80 and/or embedded processor (eP) 88 . The eRWM 80 includes embedded RAM (eRAM) and embedded ROM (eROM). The RAM in the eRAM could be SRAM or DRAM; the ROM in the eROM is preferably non-volatile memory (NVM), such as MROM, EPROM, EEPROM and flash. The eP 88 includes embedded decoder, D/A converter, decryption engine and others. An exemplary eP is embedded media player (eMP), which plays audio/video (A/V) materials. Integrated with the 3D-M 0 , the substrate-IC 0 SC can implement various functions: the eRAM can be used as a cache for the 3D-M data (referring to FIG. 17 ); the eROM can be used in the redundancy circuit and software-upgrade blocks (referring to FIGS. 25 - 26 ); the eP can be used in computer-on-a-chip (ConC) and player-on-a-chip (PonC) (referring to FIGS. 3 - 4 ). In these applications, the substrate-IC 0 SC works for the 3D-M 0 . On the other hand, the 3D-M 0 can work for the substrate-IC 0 SC. The 3D-M can carry the test data for the IC under test so that 3D-M-based self-test can be realized (referring to FIGS. 28 - 33 ).

A. Computer-on-a-Chip (ConC)

FIGS. 3A-3D illustrate several preferred computer-on-a-chip (ConC). The substrate-IC 0 SC in a ConC comprises an eRAM 82 and an eP 88 . The 3D-M 0 and the eRAM 82 form the memory space 86 of the ConC. Data from the 3D-M is first copied into the eRAM before being processed by the eP. This reconciles the speed difference between the eP and 3D-M. A preferred implementation is illustrated in FIG. 17 . This ConC hierarchy (3D-M 0 →eRAM 82 →eP 88 ) is similar to that of a conventional computer (HDD→RAM→CPU). In a conventional computer, with a large capacity, hard-disk drive (HDD) is used as the primary storage device; with a long latency (˜ms), the HDD needs a RAM as its cache. In a ConC, with a large capacity, 3D-M is used as the primary storage device; with a somewhat long latency, the 3D-M also needs RAM 82 as its cache. However, because the 3D-M latency (˜μs) is much shorter than the HDD latency, the RAM needed by the ConC is far less than that needed by a conventional computer.

In a ConC, software codes are preferably stored in the 3D-M and data can be stored in the eRAM and/or eROM. When copied into eRAM, software codes can share the same eRAM 82 with the data (FIG. 3 A), or be separated into different sectors (e.g. sector 82 a stores software codes and sector 82 b stores data) (FIG. 3 B). For the data stored in the eROM 84 , they can be either first copied into the eRAM 82 and executed from there, or executed-in-place (FIG. 3 C). To simplify the hardware design, ConC can use address-translation (FIG. 3 D). For address-translation, 3D-M 0 and eRWM 80 form a unified memory space 86 S. The address 86 A from the eP 88 is first sent to an address-translation block 86 T, which treats this address 86 A as a virtual address and translates it into a physical address 86 TA. The output of the address-translation block 86 T is connected with the input of the address-decoder 164 D for the unified memory space 86 S. Based on the physical address 86 TA, data are read out either from the 3D-M 0 or from the eRWM 80 . The details of address-translation are explained in FIG. 26 C.

In the area of content storage (electronic books, electronic maps, more particularly A/V materials), ConC can help to realize player-on-a-chip (PonC). PonC provides excellent copyright protection for content providers. Currently, contents are released in optical discs (e.g. CD, DVD). Because optical disc cannot be integrated with content players (e.g. A/V players), the original contents can be easily stolen from the interface between optical discs and content players. On the other hand, in a PonC, the 3D-M 0 —as the content carrier—is integrated with an embedded media-player (eMP) 88 MP (FIG. 4 A). The decoder 88 DE in the eMP 88 MP performs the on-chip decoding. More ideally, an on-chip D/A converter 88 DA further converts digital A/V signals 89 d into analog A/V signals 89 a . Moreover, if the original contents are “sealed” into the 3D-M “pre-sale” by mask or electrical means, the original contents are not exposed to a second party in any form and they cannot be digitally duplicated. As a result, PonC provides excellent copyright protection. PonC can help to miniaturize “digital walkman”, “wearable computer” and others. In the near future, these devices will just comprise a chip, a battery and output means (headset and/or micro-display).

For the 3DiM using 3D-MPROM to carry contents or other sensitive data, to prevent professional pirates from stealing the 3D-MPROM data from its info-via pattern by reverse-engineering means such as de-layering, the 3D-MPROM data are preferably encrypted. To take full advantage of the 3D-M's integratibility, the substrate-IC 0 SC preferably further comprises an on-chip decryption engine 88 DE and an on-chip key storage 85 (FIG. 4 B). The 3D-MPROM data are decrypted on-chip. The decrypted data 89 dd are sent to the other functional blocks 0 SCX on the 3DiM. As a result, it is very difficult to reverse-engineer the 3D-M data.

B. Shielding

In a 3DiM when a substrate circuit is running at high speed, it may interfere with the data read-out in the 3D-M. To minimize interference in certain applications, a shielding layer 10 S is preferably inserted between the substrate circuit and the data read-out line. FIGS. 5 AA- 5 CB illustrate three preferred shielding layers. FIGS. 5 AA- 5 AB are the cross-sectional view and plan view of a 3DiM with a first preferred shielding layer 10 S. This preferred shielding layer 10 S comprises a dedicated metal layer. In this metal layer, a metallic piece 0 IS covers most area of the substrate circuit 0 s and provides shielding. FIGS. 5 BA- 5 BB are the cross-sectional view and plan view of a 3DiM with a second preferred shielding layer 10 S. In this preferred embodiment, a word-line layer 20 a separates the remaining 3D-M 0 from the substrate circuit 0 s . Since they are minimum-spaced and their voltages are typically static (i.e. either at GND or at V R ), word lines 20 a —when used as the shielding layer 10 S—can shield most electromagnetic (EM) interference between the substrate circuit 0 s and the 3D-M 0 . FIGS. 5 CA- 5 CB are the cross-sectional view and plan view of a 3DiM with a third preferred shielding layer 10 S. Since the top metal layer of the substrate circuit 0 s is typically used for the power supply routing (which is static), it can also be used as the shielding layer for the substrate circuit 0 s . To minimize the EM interference between the substrate circuit 0 s and the 3D-M 0 , the spacing d between V DD supply 0 Ib 1 and GND supply 0 Ib 2 is preferably minimized. Note that in FIGS. 5 BA- 5 CB; the shielding layer 10 S uses an existing interconnect layer and no dedicated shielding layers are needed.

C. Interface Wiring

FIG. 6 AA illustrate a conventional arrangement of a 3D-M array 0 A and its contact vias 20 av - 20 hv . FIG. 6 AB is a cross-sectional view along A′A″. Viewed at the substrate-IC, these contact vias 20 av - 20 hv and the 3D-M array 0 A form a “dense net”. This “dense net” makes interfacing the substrate-IC with external world (outside the chip) very difficult.

To interface the substrate-IC with external world, embedded wire (FIGS. 6 BA- 6 BB) and bended address-selection line (FIGS. 6 CA- 6 CB) are preferably used. FIGS. 6 BA- 6 BB illustrate a preferred embedded wire 20 ei . It is particularly suitable for flip-chip, BGA and other package designs. In the 3D-M array, there are a plurality of gaps between certain address-select lines, e.g. a first gap 20 gap between word lines 20 p , 20 q and a second gap 30 gp between bit lines 30 p , 30 q (FIG. 6 BA). A landing pad 20 lp 1 is formed in the intersection of the first and second gaps 20 gp , 30 gp . The landing pad 20 lp 1 in memory level 100 , landing pad 20 lp 1 ′ in memory level 200 and contact vias 20 lv 1 - 20 lv 3 form an embedded wire 20 ei (FIG. 6 BB), which interfaces the substrate-IC to the external world. The embedded wire 20 ei can be placed nearly anywhere on the chip. Being short, it helps to maintain the circuit speed.

FIGS. 6 CA- 6 CB illustrate preferred bended address-select lines. In this preferred embodiment, word lines 20 a - 20 h are divided into two groups: Group A includes word lines 20 a - 20 d ; Group B includes word lines 20 e - 20 h . Word lines in each group are bended in such a way that interfacing gap 20 gpb is formed between contact vias 20 av - 20 dv and 20 ev - 20 hv associated with each group (FIGS. 6 CA- 6 CB). The interfacing gap allows the interfacing wires of the substrate-IC to pass through. In addition, the placement of contact vias 20 av - 20 hv could be more flexible. Their spacing d cv can be larger than that in a 3D-M based on a conventional design (in a conventional 3D-M design, d cv is equal to the spacing between address-select lines d al , referring to FIG. 6 AA). Accordingly, bended address-select lines can facilitate the layout of the address decoders.

D. Address-Decoder Fold-Back

One way to increase the 3D-M capacity is to improve its array efficiency. Array efficiency is the ratio between the area of the memory array and that of the whole chip. For a conventional transistor-based memory, because the peripheral circuit and memory array both reside in substrate, peripheral circuit is located “around” the memory array. Accordingly, its array efficiency is typically ˜60%. For a 3D-M, since its memory array is located above the substrate, its peripheral circuit can be folded-back under its memory array with the help of routing levels (referring to FIG. 14 of U.S. Pat. No. 5,835,396). As a result, the memory array can occupy nearly the whole chip area and its array efficiency can approach 100%. Moreover, for the 3D-M integrated with a substrate-IC, its routing levels can utilize the existing interconnect layers of the substrate-IC (FIG. 2 A). This simplifies the process. FIGS. 7 AA- 7 BC illustrate several preferred fold-back schemes and the routing levels involved.

FIGS. 7 AA- 7 AC illustrate a preferred fold-back scheme based on separate routing levels. This preferred embodiment comprises an interconnect 0 R with four routing levels 0 r 1 - 0 r 4 and a memory array 0 A with four address-select-line layers 20 a ′, 30 a ′, 20 a , 30 a . Each routing level ( 0 r 1 - 0 r 4 ) is separately dedicated for one address-select-line layer ( 30 a , 20 a , 30 a ′, 20 a ′, respectively) (FIGS. 7 AA- 7 AB), thus it is referred to as separate routing level. Here, the routing level 0 r 2 folds the address decoder connected with the word line 20 a back under the memory array 0 A; the routing levels 0 r 1 , 0 r 3 , 0 r 4 perform similar task. Accordingly, address decoders can be placed nearly anywhere under the memory array (FIG. 7 AC): row decoders 12 l , 12 r can be placed on its left- and right-hand sides; column decoders 18 t , 18 b can be placed on its top- and bottom- sides; for the word lines whose ends are located at the array corner, their row decoders 12 tl (connected to word lines by connecting wire 0 cw ) can be placed at the near-center position of the memory array. As a result, all peripheral circuit can be placed under the memory array 0 A. Apparently, separate routing levels support double-driven address-select lines (i.e. the address-select lines driven from both ends, e.g. word/bit lines of 3D-EPROM and word line of 3D-MPROM).

FIGS. 7 BA- 7 BC illustrate an alternate preferred fold-back scheme based on shared routing levels. As its name suggests, two levels of address-select lines share one routing level, i.e. word line 20 a and bit line 30 a share routing level 0 r 1 ′; word line 20 a ′ and bit line 30 a ′ share the routing level 0 r 2 ′ (FIGS. 7 BA- 7 BB). Similarly, the routing levels 0 r 1 ′, 0 r 2 ′ fold address decoders back under the memory array 0 A (FIG. 7 BC). It is more suitable to single-driven address-select lines (i.e. the address-select lines driven from a single end).

E. 3D-M Supporting High-Temperature Operation

In certain 3DiM applications, more particularly ConC, 3D-M needs to support high-temperature operation. At a high ambient temperature, the 3D-M based on poly- or α-silicon may have a large leakage current. In order to guarantee a normal operation, the semiconductor materials used in 3D-M cells could have large bandgap (E g ). Examples include C and SiC x . Alternatively, these semiconductor materials could be doped with elements such as C, O, N. These elements can adjust the bandgap of the semiconductor materials. Accordingly, the 3D-ROM layer 22 in FIG. 1 DA may comprise a layer of high-E g semiconductor materials, such as C, SiC x (x>0), SiO y (y>0), SiN z (z>0).

2. 3D-ROM Structure

With a simple structure and excellent manufacturability, diode-based 3D-ROM will very likely become the first 3D-M put into mass production. Moreover, its outstanding integratibility makes the 3D-ROM suitable for ConC/PonC. The present invention makes further improvement on the 3D-ROM.

A. 3D-MPROM

Among all 3D-ROM's, 3D-MPROM is the easiest to be implemented. It distinguishes a logic “0” and “1” through the absence or existence of a via. Accordingly, these vias are referred to as info-vias. The cost of a 3D-MPROM chip includes the lithographic cost for its address-select lines and info-vias. The address-select lines do not incur high lithographic cost for the following reasons: their patterns are high repetitive, and they may use phase-shift mask and mature lithography; moreover, the address-select-line mask can be shared in a large number of 3D-MPROM products and therefore, the mask cost per chip is low. In comparison, the lithographic cost for the info-via mask is higher. Fortunately, this cost can be lowered by using nF-opening mask and programmable litho-system. FIGS. 8A-8B compare 1F-opening mask and nF-opening mask during a preferred 3D-MPROM process flow.

FIG. 8A illustrates the relative placement of the conventional 1F-opening patterns with respect to the address-select-line patterns on silicon. Since the conventional info-via (e.g. 1 ca ) is located within the intersection of the word and bit lines, its dimension is preferably smaller than or equal to the width of the address-select lines (e.g. 20 c , 30 a ), which is 1F. In fact, 3D-MPROM may use larger info-vias (referring to FIGS. 9 - 10 ). FIG. 8B illustrates the relative placement of the nF-opening patterns with respect to the address-select-line patterns on silicon. Here, n=2, i.e. the dimension of info-opening (i.e. the opening for the info-via, e.g. 1 ca +) is twice the width of the address-select lines. For example, for the 3D-MPROM based on 0.25 μm technology, its info-via mask can be based on 0.5 μm technology. Moreover, adjacent openings can be merged together on a 2F-opening mask and the no accurate alignment is required during lithography. As a result, the info-opening layer incurs a fairly low lithographic cost. In the preferred embodiments of FIGS. 9-10 , nF-opening masks are used. Apparently, 1F-opening may also be used.

FIGS. 9-10 illustrate several self-aligned 3D-MPROM. In a self-aligned 3D-MPROM, the 3D-ROM layer is self-aligned with the word and bit lines and its formation does not require any individual pattern-transfer step. The 3D-ROM layer in FIG. 9 is pillar-shaped and the 3D-ROM layer in FIG. 10 is a natural junction.

FIGS. 9A-9C illustrate several preferred self-aligned pillar-shaped 3D-MPROM (SP 3D-MPROM) and their preferred process flow. In an SP 3D-MPROM, the 3D-ROM layer has a pillar shape, with one dimension equal to the word-line width and the other dimension equal to the bit-line width. The memory levels in FIGS. 9 A- 9 BD are interleaved; the memory levels in FIG. 9C are separate.

FIG. 9A illustrates an interleaved SP 3D-MPROM (ISP 3D-MPROM). In this preferred embodiment, adjacent memory levels share one address-select line. For example, memory level ML 100 shares with memory level ML 200 word line 20 a . Because the address-selection lines are shared, the layering sequences of the 3D-ROM layer in adjacent memory levels are opposite: if the layering sequence for the 3D-ROM layer 22 in ML 100 is N+, N−, P+ (in the order they are formed during process), then the layering sequence for 3D-ROM layer 22 ′ in ML 200 is P+, N−, N+. For the 3D-M cell between word line 20 a and bit line 30 c , a config-dielectric 23 , isolates the word line 20 a from the bit line 30 c . Accordingly, it represents logic “0”. For the 3D-M cell between word line 20 a and bit line 30 b , config-dielectric 23 is removed and an info-opening 24 allows current flow from the word line 20 a to the bit line 30 b . Accordingly, it represents logic “1”. Because the nF-opening mask is used, along the direction of the upper-level address-select line (word line 20 a ), the dimension of the info-opening 24 is larger than the width of the lower-level address-select line (bit line 30 b ).

During the read-out of the ISP 3D-ROM (e.g. ML 200 ), a read voltage V R is applied on word line 20 a and read current is sensed at bit lines 30 a ′- 30 c 40 . Meanwhile, the address-select lines 20 a ′, 30 a - 30 c on other memory levels are biased in such a way that no read current flows into these memory levels. For example, 20 a ′ is biased at 0V and 30 a - 30 c is biased at V R .

FIGS. 9 BA- 9 BD illustrate a preferred process flow of the ISP 3D-MPROM. First, a bit-line layer 30 a and a first 3D-ROM layer 22 are formed consecutively. Then a first etch is performed on the first 3D-ROM layer 22 and the bit-line layer 30 a to form bit-line strips. Next, gaps between the bit-line strips are filled with lower-level dielectric 26 . This is followed by a planarization step (e.g. CMP) that exposes the first 3D-ROM layer 22 (FIG. 9 BA). Alternatively, a bit-line buffer layer 26 e is formed on top of the bit-line layer 30 a and the first 3D-ROM layer 22 (FIG. 9 BA′). This bit-line buffer layer 26 e is conductive and preferably patterned by the first etch. This structure can be used in a seamless 3D-ROM cell (referring to section “Yield-enhancement techniques”).

Then a config-dielectric 23 is formed on top of the planarized lower-level dielectric 26 . If an nF-opening mask is to be used, the lower-level dielectric 26 and config-dielectric 23 preferably comprises different materials. For example, the config-dielectric 23 comprises silicon nitride or interleaved silicon oxide/nitride layers, whereas, the lower-level dielectric 26 comprise silicon oxide. Its purpose will become apparent as FIG. 9 BC is explained. This is followed by a lithography step. Photoresist 23 pr at the location of logic “0” cell (e.g. at the intersection with the bit line 30 a ) remains, while photoresist 23 pr at the location of logic “1” cell (e.g. at the intersection 24 with the bit line 30 b ) is removed (FIG. 9 BB).

After lithography, a second etch is performed on the config-dielectric 23 . Said second etch preferably has good selectivity between the config-dielectric 23 and the lower-level dielectric 26 , i.e. it can quickly remove the config-dielectric 23 but stops at the lower-level dielectric 26 . Here, along the x direction, the dimension of the info-opening 24 is larger than the width of the lower-level address-select line (bit line) 30 b . This preferred structure causes little or no performance penalty. After the second etch, a word-line layer 20 a and a second 3D-ROM layer 22 ′ are formed thereon consecutively (FIG. 9 BC). Then a third etch removes the second 3D-ROM layer 22 ′, the word-line layer 20 a and the first 3D-ROM layer 22 before it stops on the bit-line layer 30 a . Said third etch forms word-line strip (FIG. 9 BD is its cross-sectional view in the y-z plane. Note that FIGS. 9 BA- 9 BC are cross-sectional views in the x-z plane).

In the preferred process flow of FIGS. 9 BA- 9 BD, there is no individual pattern-transfer step to define the 3D-ROM layer 22 . It is formed during the first and third etches and is self-aligned with the word and bit lines. The 3D-ROM layer 22 is pillar-shaped, with its first dimension 22 wx equal to the bit-line width 30 w ( FIG. 9A ) and its second dimension 22 wy equal to the word-line width 20 w (FIG. 9 B).

FIG. 9C illustrates a separate SP 3D-MPROM (SSP 3D-MPROM). Its memory levels are separated by an inter-level dielectric 2 and no address-select lines are shared between memory levels

FIGS. 10 A- 10 ED illustrates several preferred self-aligned natural-junction 3D-MPROM (SN 3D-MPROM) and their preferred process flow. In an SN 3D-MPROM, there is no dedicated 3D-ROM layer. The diode or similar junctions are formed naturally at the intersection between word and bit lines. One part of the 3D-ROM layer is in the word line and the other part in the bit line. The memory levels in FIGS. 10 A- 10 CD are interleaved, while the memory levels in FIGS. 10 D- 10 ED are separated.

FIG. 10A illustrate an interleaved SN 3D-MPROM (ISN 3D-MPROM). Its structure resembles that of FIG. 9A except that there is no dedicated 3D-ROM layer 22 . FIGS. 10 BA- 10 BD illustrate several preferred ISN 3D-MPROM cells. In each figure, there are two memory cells 1 nj , 1 l 0 . Memory cell 1 nj is located on top of memory cell 1 l 0 and they share one electrode 20 a . Memory cell 1 nj represents logic “1” and memory cell 1 l 0 represents logic “0”.

FIG. 10 BA illustrates a natural P+/N−/N+ diode junction. For memory cell 1 nj , word line 20 a (comprising poly P+ silicon or other semiconductor materials) and bit line 30 a ′ (comprising three sub-layers: N+ poly 30 al ′, N− poly 30 a 2 ′, N− poly 30 a 3 ′) form a natural P+/N−/N+ diode junction at their intersection. It represents logic “1”. Moreover, N− poly 30 a 3 ′ can form another natural junction with the word line 20 a ′ (as illustrated in FIG. 10A but not shown here). For memory cell 1 l 0 , the existence of config-dielectric 23 between the word line 20 a and the bit line 30 a prevents the formation of a natural junction. Accordingly, it represents logic “0”.

The preferred embodiment in FIG. 10 BA can be formed by standard process: poly silicon in the address-select lines 30 a , 20 a , 30 a ′ can be formed by a standard poly process; after the formation of all address lines, a high temperature anneal activates dopants and can form excellent natural diode junctions. Since high temperature is involved, the substrate interconnects preferably comprise refractory conductors (e.g. refractory metal, their alloys, composites or even highly-doped poly).

FIG. 10 BB is similar to FIG. 10 BA except that word line 20 a comprises metallic materials (e.g. W, Pt). In this preferred embodiment, a natural Schottky diode is formed at the intersection between the word line 20 a and the bit line 30 a ′. It can also be formed by standard process.

In FIG. 10 BC, at least one metallic layer is inserted in the word and bit lines. Here, bit-line 30 a ′ comprises five sub-layers: N− poly 30 a 2 ′, N+ poly 30 a ′, metallic layer 30 a 4 ′, N+ poly 30 a 6 ′, N− poly 30 a 3 ′; word line 20 a comprise three sub-layers: P+ poly 20 a 2 , metallic layer 20 a 1 , P+ poly 20 a 3 . The insertion of metallic layers 30 a 4 ′, 20 a 1 can significantly reduce the parasitic series resistance of the address-select lines and therefore, improve the read speed. Alternatively, a first address-select-line layer (e.g. word line) comprises metallic materials and a second address-select-line layer (e.g. bit line) comprises semiconductor materials.

Similarly, poly bit lines in FIG. 10 BB may also comprise metallic layers 30 a 3 , 30 a 4 ′. This is illustrated in FIG. 10 BD. Alternatively, a metallic ion-implant can be performed to the poly address-selection lines of FIGS. 10 BA- 10 BB so that their parasitic series resistance can be reduced. This method does not require extra metallic layers and can lower the manufacturing complexity.

FIGS. 10 CA- 10 CD illustrate a preferred process flow of a INJ 3D-MPROM. It is similar to FIGS. 9 BA- 9 BD. In FIG. 10 CA, bit-line strips 30 a are formed by a first etch and lower-level dielectric 26 is planarized. In FIG. 10 CB, photoresist 23 pr is applied to config-dielectric 23 and exposed to the nF-opening mask. In FIG. 10 CC, the config-dielectric 23 is removed by a second etch at the desired location 24 and word-line layer 20 a is formed. In FIG. 10 CD, the word-line strips 20 a are formed by a third etch (FIG. 10 CD is a cross-sectional view in the y-z plane; FIGS. 10 CA- 10 CC are cross-sectional views in the x-z plane). This preferred process flow is very simple. For the preferred embodiments of FIGS. 10 BA- 10 BB, their address-select lines comprise one material, the etching of which can be easily implemented.

FIG. 10D illustrates a separate SN 3D-MPROM (SSN 3D-MPROM). It comprises two separate memory levels ML 100 and 200 , separated by inter-level dielectric 27 .

FIGS. 10 EA- 10 ED illustrate several preferred SSN 3D-MPROM cells. Because word/bit lines are not shared between adjacent memory levels, their structures are simpler than those of FIGS. 10 BA- 10 BD. FIG. 10 EA illustrates a preferred natural P+/N−/N+ diode junction 1 nj formed between word line 20 a and bit line 30 b . FIG. 10 EB illustrates a preferred natural Schottky junction 1 nj ′. FIG. 10 EC is similar to FIG. 10 EA, except that metallic layers 20 a 1 , 30 b 3 are inserted into the poly lines. Similarly, it is also feasible to insert metallic layers into just one address-select-line level (preferably word lines). FIG. 10 ED is similar to FIG. 10 EB, expect that metallic layers 30 b 3 are inserted into bit line 30 b . These metallic layers can reduce the parasitic series resistance of address-select lines and improve the read speed. Alternatively, a metallic ion-implant can be performed to the poly lines of FIGS. 10 EA- 10 EB.

B. 3D-EPROM Cells

FIGS. 11 BA- 11 BB illustrate two preferred 3D-EPROM cells with metal/semiconductor address-select lines. It borrows the concept from FIGS. 10 BC- 10 BD, 10 EC- 10 ED, i.e. metallic layers 20 a 1 , 30 c 3 are inserted into the poly lines; or a metallic ion-implant is performed to the poly lines. They can reduce the parasitic series resistance of the address-select lines. Accordingly, under the same programming condition, the programming current is larger and therefore, programming becomes faster and more reliable. Moreover, with a smaller RC delay, read speed can significantly be improved. Antifuse layer 22 a can be located between the N+ poly 30 c 2 and N− poly 30 c 1 of FIGS. 11A-11B , or between P+ poly 20 a 2 and N− poly 30 c 1 of FIG. 11A , or between word line 20 a and N− poly 30 c 1 of FIG. 11 B.

C. Inverted-U Link

Many address-selection lines in FIGS. 9-11 (e.g. 30 a ′ of FIGS. 10 BA- 10 BD) are composite lines. Composite lines comprise at least a highly-conductive layer and a bottom lightly-doped, (semiconductor) layer. As its name suggests, the bottom lightly-doped layer is located at the bottom of the composite line. Besides the 3D-M, composite lines can also be used in other integrated circuits. To contact a line with a via, the conventional approach makes the contact from below (e.g. FIG. 2 A). For the composite line, contact-from-below cannot make good ohmic contact. Accordingly, the composite line is preferably contacted on top and/or on sidewall by an inverted-U link. This invert-U link makes direct contact to the highly-conductive layer in the composite line. As a result, a small contact resistance can be achieved. FIGS. 12 AA- 12 CB″ illustrate several preferred inverted-U links and their preferred process flows.

FIGS. 12 AA- 12 AB illustrate two preferred inverted-U link for a first composite line 30 . Here, the first composite line 30 has a bi-layer structure, i.e. it comprises a highly-conductive layer 30 mc and a bottom lightly-doped layer 30 lda . In FIG. 12 AA, via 30 v makes contact with the highly-conductive layer 30 mc of the first composite line 30 on top through a first inverted-U link 30 uc . In FIG. 12 AB, via 30 v makes contact with the highly-conductive layer 30 mc of the first composite line 30 on top and on sidewall through a second inverted-U link 30 bc.

FIGS. 12 BA- 12 BB illustrate two preferred inverted-U link to a second composite line 30 ′. The second composite line 30 ′ has a tri-layer structure, i.e. it further comprise a top lightly-doped layer 30 ldb and the highly-conductive layer 30 mc is sandwiched between both lightly-doped layers 30 lda . 30 ldb . In FIG. 12 BA, via 30 v makes contact with the highly-conductive layer 30 mc of the second composite line 30 ′ on top through a third inverted-U link 30 uc ′. In, FIG. 12 BB, via 30 v makes contact with the highly-conductive layer 30 mc of the second composite line 30 ′ on top and on sidewall through a fourth inverted-U link 30 bc ′. Note that a portion of the top lightly-doped layer 30 lda is removed to expose a portion of the highly-conductive layer 30 mc.

FIGS. 12 CA- 12 CC illustrate a preferred process flow for the first inverted-U link. After the formation of the via 30 v , the first composite line 30 is formed and it is covered with a dielectric 30 vd (FIG. 12 CA). At this point, there is no contact between the via 30 v and the first composite line 30 . Two openings 30 v 1 , 30 v 2 are formed in the dielectric 30 vd . The opening 30 v 1 exposes the via 30 v and the opening 30 v 2 exposes a portion of the first composite line 30 on top (FIG. 12 CB). Then conductive materials 30 uc 1 are filled in these opening (FIG. 12 CC). Another metallization step completes the structure of FIG. 12 AA.

The preferred process flow for the inverted-U link of FIG. 12 AB is similar to that for FIG. 12 AA, except that via 30 v 3 also exposes the sidewalls of the first composite line 30 (FIG. 12 CB′). This facilitates contact to the first composite line 30 on its sidewalls.

The preferred process flows for the inverted-U link of FIGS. 12 BA- 12 BB are similar to those for FIGS. 12 AA- 12 AB, except that during the formation of vias 30 v 2 , a portion of the top lightly-doped layer 30 ldb is etched away and a portion of the highly-conductive layer 30 mc is exposed. Moreover, techniques such as dual damascene can be used. FIG. 12 CB″ illustrates a preferred inverted-U link using dual damascene before the filling of conductive materials. Besides the openings 30 v 1 , 30 v 2 , a trench 30 t is formed in the dielectric 30 vd.

3. 3D-M Speed

Using 3D-ROM as an example, the present invention makes further improvement on the 3D-M speed by optimizing its transistor-level designs, more particularly, the designs of 3D-M core, 3DcM (cached 3D-M) and programming circuits. For the design perspective, techniques such as sense-amplifier (S/A), full-read mode and self-timing are preferably used; from the systems perspective, 3DcM is preferably used to hide the 3D-M latency. Accordingly, even though the performance of a single 3D-M cell cannot yet compete with the conventional memory, through system integration, its collective performance can match that of the conventional memory, even excel. To increase the write speed, parallel programming is preferred.

A. 3D-M Core

FIG. 13A illustrates the I/O ports of a preferred 3D-M core 0 . A 3D-M core includes the 3D-M array and its basic peripheral circuit. The input signals include row address AS 2 and read-initiating signal RD 4 . The output signals include data output DO 8 and data-ready signal RY 6 .

FIG. 13B illustrates a basic block diagram of the preferred 3D-ROM core 0 . It comprises a 3D-ROM array 0 A, a sense amplifier (S/A) block 18 , a trip-voltage (V M ) generating block 14 , a row decoder 12 , a bit-line disable block 18 ′, a bias block 16 and an address latch 121 . Among these, the 3D-ROM unit array 0 A comprises N WL word lines ( 20 c . . . ) and N BL bit lines ( 30 c . . . ). At each intersection between the word and bit lines, the existence of a diode indicates a logic “1”; the absence indicates a logic “0”. Here, bit lines 30 a - 30 d that store valid data bits are referred to as data bit line. The S/A block 18 amplifies the small analog signals on a bit line 30 c and converts it into a logic signal 8 . Controlled by S/A-enable signal SE 5 , the S/A block 18 samples data only when SE 5 is asserted. The V M -generating-block 14 generates the trip voltage V M 7. V M is the input bias voltage at which the S/A is very sensitive to input change. The row decoder 12 selects a single word line based on input address 21 . When RY 6 is asserted, both the row decoder 12 and the bit-line disable block 18 ′ are disabled, i.e. all word and bit lines are pre-/dis-charged to V M . The bias block 16 generates SE 5 through a timing signal TS 8 T. At the beginning of a read cycle, SE 5 is low and no data S/A's are enabled. When TS 8 T switches to high, SE 5 enables data S/A's and starts data sampling. The data sampling lasts until all output 8 becomes valid. Then RY 6 is issued and data sampling is stopped. This concludes a read cycle. Its timing diagram is illustrated in FIG. 16 .

During a major portion of a read cycle, the voltage rise on each bit line is too small to trigger its S/A. If all S/A's are turned on during this period, they would be consuming a lot of power while their outputs are not valid. It is preferably to just leave a small number of S/A's on, which monitor the voltage change on their bit lines. Only when they sense a large enough voltage change, other S/A's are turned on and start to sample. Accordingly, the majority of S/A's are turned on only during a small fraction of the read cycle, thus saving power. This is the concept behind self-timing.

FIG. 13C illustrates a preferred implementation of self-timing. A first timing bit line 30 T is added to the 3D-ROM array 0 A. It is preferably the bit line located farthest from any row decoder. It has a diode connection ( 1 a T . . . ) with every word line ( 20 a . . . ) it crosses. During read, the voltage rise on the first timing bit line 30 T is preferably slower than that on any data “1” bit lines (data “1” bit line is a data bit line that reads out a logic “1”). Accordingly, when the first timing S/A 17 T is triggered, the voltage change on all data “1” bit lines should have been large enough to trigger their respective S/A 17 a - 17 d . Then the data S/A 17 a - 17 d are turned on and start to sample data.

FIG. 13C also illustrates the S/A block 18 , the bias block 16 , the row decoder 12 and the bit-line disable block 18 ′ in more details.

The S/A block 18 comprises at least a first timing S/A 17 T and a plurality of data S/A 17 a - 17 d . When the voltage on a bit line exceeds a threshold voltage V T , its S/A output switches to high. Here, the data S/A 17 a - 17 d are controlled by SE 5 and they only sample data when SE 5 is high. Since the first timing S/A 17 T keeps monitoring the voltage on the first timing bit line 17 T during read, its bias signal 5 T stays constant during read.

The bias block 16 generates SE 5 based on the output 8 T from the first timing S/A 17 T. It comprises a timing circuit 15 T and a bias-generating circuit 15 B. The timing circuit 15 T controls timing signal 15 d , and the bias-generating circuit 15 B generates the biases SE 5 and 5 T. When 15 d is low, SE 5 becomes asserted.

The row decoder 12 comprises a standard row decoder 12 ′ and a plurality of row-decoder disable blocks 11 a - 11 d . When RY 6 is high, row decoder 12 is disabled and all word lines are shorted to V M 7 ; when RY 6 is low and 20 a ′ is high, word line is connected to V R and the 3D-M is switched to the read mode.

In the bit-line disable block 18 ′, each bit line is connected to V M 7 through a switch (e.g. transistors 17 a ′- 17 d ′). The controls of all switches are shorted to RY 6 . When RY 6 is high, all bit lines are shorted to V M 7 . The bit-line disable block 18 ′ enables the full-read mode for the 3D-M.

Referring now to both FIGS. 13B and 13C , a preferred 3D-ROM read-out flow is disclosed. Its timing diagram is illustrated in FIG. 16 . The data are preferably read out in a full-read mode, i.e. all data on a single word line are read out in a single read cycle. To be more specific, the 3D-ROM core 0 is initially at its default state, i.e. all word/bit lines are biased at V M and all S/A's are disabled. On the rising edge of RD 4 , address latch 121 captures AS 2 (e.g. 00) and sends it to the row decoder 12 . Then the corresponding word line 20 a raises its voltage to V R and starts to charge every bit line ( 30 a . . . ) that has a diode connection with it. At this moment, all data S/A's 17 a - 17 d are still off, but the first timing S/A 17 T keeps monitoring the voltage on the first timing bit line 30 T. When it exceeds V T , 8 T switches to high and SE 5 becomes asserted. Then all data S/A's 17 a - 17 d are turned on and start to sample the voltage on their respective bit lines 30 a - 30 d . After DO 8 is generated, SE 5 returns to low and all data S/A's returns to off. Since the word line 20 a does not need to stay at V R any more, RY 6 is issued and the 3D-ROM core 0 returns to its default state. This concludes one read cycle T.

FIGS. 14A-14G disclose the designs of several circuit blocks used in the 3D-ROM core. FIGS. 14 A- 14 CC illustrate several differential S/A's. FIGS. 14 DA- 14 DD disclose a second timing bit line and the design of the timing circuit 15 T. FIGS. 14E-14G illustrate a bias-generating circuit 15 B, row-decode disable block 11 a and V M -generating-block 14 .

To achieve noise immunity, S/A preferably uses differential S/A. Besides taking the bit-line voltage as one input, differential S/A needs a reference voltage. It can be provided by a dummy bit line. FIG. 14A illustrates two bit lines under read ( 30 a , 30 z ), a dummy bit line 30 D and their connections with two differential S/A's ( 17 a , 17 z ). The dummy bit line 30 D can be shared by a number of S/A's. It has a diode connection 1 a D at each cross-point with word lines. During read, the value of the dummy-bit-line voltage is preferably between those on the data “1” and “0” bit lines.

FIG. 14 BA is a circuit diagram of a first preferred differential S/A core 17 C. It uses an NMOS input pair 51 a , 51 b and a mirrored PMOS load pair 51 d , 51 e . Its power supplies include V S/A and GND. Note that V S/A may be different from V dd . Bias signal B controls the tail current through NMOS 51 c . FIG. 14 BB illustrates a preferred data S/A based on the first preferred S/A core 17 C. It further comprises a latch 17 L formed by an NMOS 51 g and an inverter 51 h . Through latch signal 5 ′, NMOS 51 g is turned on when SE 5 becomes high and turned off before SE 5 becomes low. Accordingly, even during the period when the first S/A core 17 C does not sample data, output 8 a still keeps its value. FIG. 14 BC illustrates a preferred first timing S/A based on the first preferred S/A core 17 C. It always samples data. Inverter pair 51 i , 51 j form a latch 17 TL and inverters 51 l , 51 m adjust the waveform shape. At the being of each read cycle, NMOS 51 k clears the latch 17 TL under the control of RD 4 (i.e. equalization).

FIG. 14 CA is a circuit diagram of a second preferred differential S/A core 17 C′. Different from FIG. 14 BA, it uses a cross-coupled PMOS load pair 52 d , 52 e . Bias signal B controls the tail current through NMOS 52 c . When B is low, the outputs o+, o− of the second preferred S/A core 17 C′ keep their values right before B is turned low. Thus, this S/A itself works as a latch. FIG. 14 CB illustrates an alternate preferred data S/A based on the second preferred S/A core 17 C′. Inverter 52 f adjusts the waveform shape. FIG. 14 CC illustrates an alternate preferred first timing S/A based on the second preferred S/A core 17 C′. It always samples data during read. At the beginning of each read cycle, NMOS 52 g clears the second preferred S/A core 17 C′ under the control of RD 4 (i.e. equalization).

FIGS. 14 DA- 14 DD illustrate several preferred timing circuits 15 T. Combined with the bias-generating circuit 15 B, the tiring circuit 15 T controls SE 5 of all data S/A's. When 8 T is raised to high, it raises SE 5 and enables all data S/A's to sample data; then after a delay, i.e. when all data S/A's have acquired valid data, it lowers SE 5 and stops all data S/A's from sampling. To realize this delay, the preferred embodiment of FIG. 14 DA adds a second timing bit line 30 T′ to the 3D-M array, whose S/A 17 T′ controls the delay. Here, the second timing bit line 30 T′ has a diode connection 1 a T′ at each cross-point with word lines. Its S/A 17 T′ is slightly slower than data S/A. When its output 8 T′ switches, all output data should be ready and all data S/A's can stop sampling. With the help of the second timing bit line 30 T′, the power consumption can be lowered too. Note that the signal from the first timing bit line starts the data sampling for data S/A, while the signal from the second timing bit line ends the data sampling for data S/A FIG. 14 DB illustrates a preferred timing S/A 17 T′ for the second timing bit line 30 T′. Compared with the data S/A of FIG. 14 BA, either its output drives an extra capacitance 51 C, or the channel length of at least one of its transistors is longer. These and other designs can slow down this timing S/A 17 T′.

FIG. 14 DC illustrates a preferred timing circuit 15 T. The output 8 T′ from the second timing bit line 30 T′ can be directly sent out as RY 6 . Combined with the output 8 T of the first timing bit line 30 T, 8 T′ generates the bias control signal 5 d , which in turn controls SE 5 through the bias-generating circuit 15 B (referring to FIG. 14 E). FIG. 14 DD is an alternate preferred timing circuit 15 T. Compared with FIG. 14 DC, it provides a state-control signal 6 E for external circuits (e.g. circuits inside the 3DiM but outside the 3D-M). When 6 E is asserted, 3D-M is forced into its default state (i.e. all word and bit lines are shorted to V M ) and cannot perform any operation. This mode is referred to as “soft-off” mode. In the “soft-off” mode, no power is consumed by the 3D-M; when needed, the 3D-M can be quickly put into action by grounding 6 E. Compared with “hard-off” mode (i.e. all word and bit lines are grounded), the 3D-M in the “soft-off” mode can “wake-up” faster. This preferred “soft-off” design can be incorporated in many applications, such as the word-line redundancy circuit and flexible-code block (when the word line under read is defective or its data need to be upgraded), or in the 3D-M-based IC testing (when the circuit-under-test is under normal operation).

FIG. 14E illustrates a preferred bias-generating circuit 15 B. Current source 53 a can be on-chip or provided externally. The bias voltage 5 T is generated by a diode-connected NMOS 53 b . When 5 d is low, 5 T is sent to SE 5 ; when 5 d is high, SE 5 is grounded.

FIG. 14F illustrates a preferred row-decoder disable circuit 11 a . When RY 6 is high, NMOS 54 b is turned on and the word line 20 a is shorted to V M 7 . When RY 6 is low and 20 a ′ is high, PMOS 54 c is turned on and the word line 20 a is shorted with the V R . It is to be understood that V R does not have to be equal to V dd (referring to FIG. 19 CA).

FIG. 14G illustrates a preferred V M -generating block 14 . It uses the same S/A core 17 C ( 55 a ) as the data S/A. It further comprises a voltage regulator (including op-amp 55 b and driving NMOS 55 c ). With all inputs and outputs shorted together, the S/A core 55 a generates V M 7 ′, which is ˜V S/A /2. The voltage regulator maintains the output 7 at V M while providing sufficient current. Accordingly, V M 7 is a constant dc-source.

Referring now to FIGS. 15 AA- 15 AD, various aspects of the bit-line voltage timing characteristics are disclosed. As illustrated in FIG. 15 AA, after the voltage on the word line 20 y is raised to V R , the word line 20 y starts to pump current into bit line 30 j through a diode 13 d . The voltage on the bit line 30 j then starts to rise from its initial value V M . The rise rate depends on the rate at which the diode current charges up the parasitic capacitance 1 j C of the bit line 30 j . In general, this parasitic capacitance 1 j C include: the coupling capacitance 1 j 0 between the word line 20 x and the bit line 30 j (for a “0” cell), the junction capacitance 1 j 2 of the reverse-biased diode 1 zj (for a “1” cell), the sidewall coupling capacitance 1 j 3 , 1 j 4 to the adjacent bit lines 30 i , 30 k , and the coupling capacitance 1 j 1 with other interconnection layers. Since the voltage on the bit line 30 j is a little above V M while all other word lines 20 x , 20 z (excluding the word line under read 20 y ) are at V M , certain leakage current flows from the bit line 30 j to other word lines 20 z through the reverse-biased diode 1 zj . The discharging effect on the bit line 30 j from this leakage current counters the charging effect from the word line 20 y.

The equivalent circuit used to simulate the bit-line voltage timing characteristics is illustrated in FIG. 15 AB. The voltage change ΔV b on the bit fine 30 j is affected by three components: diode 1 yj , parasitic capacitance 1 j C and equivalent diode 1 j D. Equivalent diode 1 j D comprises n diodes in parallel, where n is the number of diodes that the bit line 30 j is connected with (except the one that is charging the bit line). In the worst case, n is equal to N WL− 1 . The static equilibrium voltage ΔV be on the bit line 30 j is reached when the forward current of the diode 1 yj is equal to the reverse current of the equivalent diode 1 j D.

FIG. 15 AC illustrates the, current-voltage characteristics (IV) of the diode 1 yj . Preferably, its forward current I f (V) 1 f is much larger than its reverse current I r (V) 1 r . ΔV be can be found out by graphical means: first multiply the reverse current I r (V) 1 r by (N WL− 1 ); then shift it right by V R −V M , this forms curve 1 rs ; the cross-point between 1 rs and 1 f is ΔV be . Mathematically, ΔV be can be expressed as,

I f ( V R −V M −ΔV be )=( N WL −1)× I r (Δ V be )≈ N WL ×I r (ΔV be )  eq.(1)

FIG. 15 AD is the bit-line voltage timing diagram. ΔV b eventually reaches ΔV be . At time τ, ΔV b exceeds V T and triggers the S/A. At this moment, output data becomes valid. For the bit line 30 j , the time it takes for ΔV b to reach V T is its latency τ 30j , which can be expressed as,

τ 30j ˜V T ×C 30j /I f   eq. (2)

As illustrated in FIGS. 13C , 14 A, the timing characteristics of the first timing bit line and dummy bit line are different from that of the data bit lines. Accordingly, their designs are preferably different from that of the data bit line. FIGS. 15 BA- 15 CC explain and illustrate several preferred designs. FIG. 15 BA illustrates a data bit line 30 a and a reference bit line 30 r . The reference bit line 30 r could be a first timing bit line or a dummy bit fine. During read, the voltage change ΔV 30r on the reference bit line 30 r is preferably slower than the voltage change ΔV 30a on the data bit line 30 a . For the dummy bit line, preferably ΔV 30r ˜ΔV 30a /2 (FIG. 15 BB). According to eq. (2), this can be achieved by increasing the parasitic capacitance 1 r C of the reference bit line 30 r . FIGS. 15 CA- 15 CC illustrate several preferred reference bit lines.

FIG. 15 CA illustrates a first preferred reference bit line 30 r . It is wider than data bit line 30 a . Thus, it has a larger parasitic capacitance. FIG. 15 CB illustrates a second preferred reference bit line 30 r . It comprises two shorted sub-bit lines 30 r 1 , 30 r 2 . Each of these sub-bit lines has the same width as the data bit line 30 a . The sub-bit line 30 r 1 has diode connection 1 ar 1 with every word line it crosses, whereas, the sub-bit line 30 r 2 has no diode connection with these word lines. Accordingly, the reference bit line 30 r has a larger parasitic capacitance and its voltage rise rate is slower. Note that the length of the sub-bit line 30 r 2 can be adjusted by layout. FIG. 15 CC illustrates a third preferred reference bit line 30 r . It is physically connected with a physical capacitor 1 r 0 . The physical capacitor 1 r 0 can be a MOS capacitor (including the S/A input capacitance), metal capacitor or other conventional capacitors. They can increase the latency τ.

FIG. 15D illustrates a preferred implementation of data bit lines, dummy bit lines and timing bit lines in a 3D-M array. In this preferred embodiment, there are two bit-line groups D 1 , D 2 . Within each bit-line group (D 1 ), all data bit lines share one dummy bit line ( 30 D). Each dummy bit line ( 30 D) comprises two sub-bit lines 30 D 1 , 30 D 2 . The 3D-M array further comprises a first timing bit line 30 T and its dummy timing bit line 30 TD. The first timing bit line 30 T comprises two sub-bit lines 30 T 1 , 30 T 2 , and the dummy timing bit line 30 TD comprises four sub-bit lines 30 TD 1 - 30 TD 4 . This preferred embodiment further comprises a second timing bit line 30 T′. It comprises only one bit line but its S/A 17 T′ is slower. Apparently, the voltage rise on the dummy bit line 30 D and the first timing bit line 30 T is slower than that on the data bit line 30 a ; the voltage rise on the dummy timing bit line 30 TD is even slower.

Alternatively, the dummy bit line 30 D and the first timing bit line 30 T may take a simpler form. Because it needs to drive a large number of data S/A's, whose input capacitance can significantly slow down the voltage rise, the dummy bit line 30 D may comprise only one sub-bit line. On the other hand, the first timing bit line 30 T may also comprise only one sub-bit line. In this case, its timing S/A 17 T is preferably slow, but should be faster than the timing S/A 17 T′ of the second timing bit line 30 T′.

FIG. 16 is a preferred timing diagram of various signals in the preferred 3D-ROM core 0 . At time τ 30a , the voltage change on the data bit line 30 a exceeds the V T of its S/A 17 a . However, since its S/A 17 a is not turned on, there is no valid data on the output. At time t1, the voltage change on the first timing bit line 30 T becomes large enough to trigger its S/A 17 T. This means that the 3D-ROM core 0 is ready to sample data. SE 5 is then asserted and all data S/A's are put to work. At time τ, the second timing bit line 30 T′ triggers its S/A 17 T′. This means that all data are ready. All data S/A's are then turned off. This concludes the read cycle.

Eq. (2) and FIG. 15 AA provide a set of design guidelines for a preferred 3D-ROM. To reduce the latency, the bit-line parasitic capacitance 1 j C is preferably made small. Since a major component of 1 j C is the sidewall coupling capacitance 1 j 3 , 1 j 4 , the 3D-ROM preferably uses thin bit lines. Even though thin bit lines have a larger series resistance, because the dominating portion of the resistance that determines the latency comes from the 3D-ROM layer, the larger resistance from the thin bit lines has little adverse effect on the latency. On the other hand, in the full-read mode, the word line under read carries the read current for all bit lines, which is typically large. To reduce the series voltage drop and avoid electro-migration, the 3D-ROM preferably uses thick word lines. A preferred 3D-ROM structure with thick word lines ( 20 a ) and thin bit lines ( 30 i , 30 j ) is illustrated in FIG. 2 A.

B. Cached 3D-M (3DcM)

The performance of a single 3D-M cell cannot yet compete with the conventional memory. Through system integration (e.g. using 3DiM), the potential of the 3D-M can be full exploited. Collectively, the 3D-M performance can match that of the conventional memory, even excel. Cached 3D-M (3DcM) is a good example of 3DiM. It comprises a 3D-M and an eRAM integrated with said 3D-M. 3DcM can speed up the 3D-M read-out by hiding its latency. To the external circuit, 3DcM can be viewed as an individual memory: the eRAM is formed in the substrate; the 3D-M is stacked on top of the eRAM; and the eRAM keeps a copy of data from the 3D-M. When the external circuit searches data from the 3DcM, it reads from the eRAM first. In the case of a hit, the data are read out from the eRAM; otherwise the data are read out from the 3D-M. Accordingly, the eRAM works as a cache for the 3D-M. For hit, the 3DcM latency is equal to the eRAM latency and therefore, the external circuit cannot sense the 3D-M latency; for miss, the 3DcM latency is close to that 3D-M latency. If the eRAM has a large capacity, the chance for hits is large and therefore, the average latency becomes small. On the other hand, the 3DcM bandwidth is typically controlled by the eRAM.

The read operation in a 3DcM is similar to the cache operation in a conventional computer. FIGS. 17A-17G disclose preferred internal data flows in a 3DcM in details. FIG. 17A illustrates the I/O ports of a preferred 3DcM 0 C. It includes input address AS 73 , 3DcM read-initiating signal cRD 75 , 3DcM data-ready signal cRY 77 , clock signal CK 71 , and data output DO 79 .

FIG. 17B is a block diagram of the preferred 3DcM 0 C. It comprises a 3D-M core 0 , column decoder 70 , eRAM 72 , control block 74 and output selection-block 76 . In this preferred embodiment, the size of the 3D-M core 0 is 1024×1024. During read, a page (1024 bits) is selected from the 3D-M array based on the row address 2 (i.e. the first 10 bits of AS 73 [13:4]) and sent to output 8 . Here, a 3D-M page comprises all data on a single word line in a 3D-M unit array. The column decoder 70 selects a word (64 bits) from this output page (1024 bits) based on the column address 2 c (i.e. the last 4 bits of AS 73 [3:0]). The selected word and the corresponding address are copied into the eRAM 72 . The control block 74 controls the data flow from the 3D-M core 0 to the eRAM 72 . For those skilled in the art, the control block 74 can be easily designed based on the preferred data flow of FIG. 17 D. The output selection-block 76 determines whether the output data 79 come from the column decoder 70 or from the eRAM 72 .

FIG. 17C illustrates a preferred eRAM 72 . It comprises a read-write-enable port R/W 74 r and a hit/miss port H/M 72 h . It further comprise an eRAM data block 72 D and an eRAM tag block 72 T. The eRAM data block 72 D keeps a copy of the data from the 3D-M core 0 and the eRAM tag block 72 T keeps the address tag for the data stored in the corresponding row in the eRAM data block 72 D. In this preferred embodiment, the size of the eRAM data block 72 D is 64×64 and the size of the eRAM tag block 72 T is 8×64. The first 8 bits 2 a of AS 73 [13:6] are stored in the eRAM tag block 73 T and the last 6 bits of AS 73 [5:0] are used as the column address 2 b for the eRAM 72 . The eRAM 72 further comprises a comparator 72 C. During read, it compares the tag 72 to from the eRAM tag block 72 T with 2 a . If they match, it is a hit and the output H/M 72 h becomes high; otherwise, 72 h stays low.

FIG. 17D discloses a preferred 3DcM read flow. First, upon receiving cRD 75 , AS 73 is sent to the eRAM 72 and the eRAM-read is enabled (step 91 ). The next step depends, on the value of the H/M 72 h (step 92 ): for hit, data 79 a from the eRAM 72 are directly sent to the output 79 (step 97 ) and cRY 79 is issued (step 98 ); for miss, data are be read out from the 3D-M core. This involves the following steps: first RD 4 of the 3D-M core 0 is issued (step 93 ); then a page is read out from the 3D-M and RY 6 is issued (step 94 ); the eRAM-write is enabled, a word 79 a is selected from the column decoder 70 , this word 79 a and its address 2 b are copied into the eRAM 72 (step 95 ); then data 79 a or 79 b are sent to the output 79 (step 96 ) and cRY 79 is issued (step 98 ).

At the step 96 , the data read-out can be “read-during-copy”, i.e. data are read right after the column decoder 70 and during the data transfer from the 3D-M core 0 to the eRAM 72 . This results in a shorter latency. FIG. 17 EA illustrates a preferred output selection-block 76 corresponding to this scheme. It uses a multiplexor 76 M, which selects between the data 79 a from the column decoder 70 (for miss) or the data 79 b from the eRAM 72 (for hit), based on the selection signal 79 s (typically controlled by H/M 72 h ).

Alternatively, “read-after-copy” can be used. In “read-after-copy”, data are only read out from the eRAM 72 , for either hit or miss. This scheme facilitates redundancy and software upgrade. FIG. 17 EB illustrates a preferred read flow. It is part of the step 96 of FIG. 17 D. After the 3D-M data are copied into the eRAM 72 , the eRAM read-out is repeated (including the steps 91 , 92 , 97 of FIG. 17 D). To be more specific, after the step 95 , AS 73 is sent to the eRAM 72 again and data are read (step 96 a ). Since this read is a sure “hit”, i.e. H/M 72 h is certainly high (step 96 b ), data 79 b from the eRAM 72 is sent to the output 79 (step 96 c ). FIG. 17 EC illustrates a preferred output selection-block 76 corresponding to this scheme. With all output data coming from the eRAM 72 , this output selection-block 76 simply uses a transmission gate 76 T to control the data flow from the eRAM 72 to the output 79 .

The preferred 3DcM in FIGS. 17 B- 17 EC is based on “word-copy”, i.e. a word (64 bits) from the output page (1024 bits) is copied into the eRAM 72 (other words in that page might be wasted). To fully utilize the data read out each time, a “page-copy” scheme is preferred, i.e. all words in the output page are copied into the eRAM 72 . It maximizes the read efficiency. FIG. 17F illustrates a preferred 3DcM using the “page-copy” scheme. Different from FIG. 17B , the column address 2 c ′ does not use the last 4 bits of AS 73 , instead it is generated internally by the control block 74 ′. For those skilled in the art, the control block 74 ′ can be easily designed based on the preferred data flow of FIGS. 17D , 17 G. FIG. 17G illustrates a preferred column-address generating flow. It is part of the step 95 of the FIG. 17 D. After the step 94 , under the control of 74 ′, the column address 2 c ′ is incremented in such a way that all words in the output page can be scanned over (step 95 a ). Then the word corresponding to 2 c ′ and 2 c ′ itself are copied into the eRAM 72 ′ (step 95 b ). Repeat the steps 95 a , 95 b until 2 c ′ reaches a predetermined maximum value (step 95 c ). As a result, all words in the output page are copied into the eRAM 72 ′. FIG. 17H illustrates a preferred eRAM 72 ′ used in the “page-copy” scheme. In this preferred embodiment, the size of the eRAM data block 72 D is still 64×64, but it is divided into four eRAM sectors. Each eRAM sector is 64×16 in size and it stores data from a whole page (1024 bits). Each eRAM sector uses one tag row. Accordingly, the size of the eRAM tag block can be 8×4.

C. Write Speed

Users of 3D-EPROM can program the chip. In order to reduce the chip programming time, a plurality of memory cells are preferably programmed at the same time. This is the concept of parallel programming. FIG. 18A illustrates a preferred implementation of parallel programming. In this preferred embodiment, cells 1 cb and 1 cc are simultaneously programmed. During programming, the voltage on the word line 20 c is V pp ; the voltages on the bit lines 30 b , 30 c are 0; the voltages on all other address-select lines are V pp /2. Accordingly, the voltages applied on the cells 1 cb , 1 cc are V pp and these cells are programmed at the same time. To lower the voltages on at least two bit lines to 0, column decoder is preferably a parallel-decoder (FIG. 18 B). It comprises two sub-decoders 70 a , 70 b . These decoders share a same column address 2 C. They could be located side-by-side or inter-leaved. In this preferred embodiment, they are mirrored. The column address 2 C (e.g. “1”) is fed into both sub-decoders 70 a , 70 b . This lowers the voltage on the bit lines 30 b , 30 c to 0. Accordingly, the voltage requirement of FIG. 18A is met.

In order to reduce the number of package pins, U.S. Pat. No. 6,385,074 suggests using an on-chip V pp -generating-block. This V pp -generating-block generates the programming voltage V pp from the chip power supply V dd . This makes sense if the 3D-M needs frequent programming. However, for the “write-once” 3D-M's, they are not programmed as frequently. Moreover, for the 3D-EPROM's carrying contents (e.g. PonC of FIG. 3 ), they are typically programmed in factory (e.g. by content providers). During usage, customers just read, but not write. For these applications, the on-chip V pp -generating-block is unnecessary. Furthermore, the saved chip space can be used to accommodate other functions. FIG. 18C illustrates a preferred 3D-M with V pp -bonding pads 12 P, 70 P. These bonding pads are used to feed the external programming voltage. For the factory-programmed content-carrying 3D-EPROM, since they are typically programmed at the wafer level, these bonding pads do not need to be bonded out. Accordingly, the number of package pins required for the chip is reduced.

4. Unit-Array Capacity

As illustrated in FIGS. 19 AA- 19 AB, the unit-array capacity of a 3D-M can strongly impact its integratibility. With a large unit array, few unit arrays (e.g. 0 A) are needed on a 3D-M chip (FIG. 19 AA). On the other hand, with a small unit array, a large number of unit arrays (e.g. 0 Aa- 0 Ai) are needed (FIG. 19 AB). Because their peripheral circuits reside in the substrate, more unit arrays on a chip means that the substrate becomes more fragmented. A fragmented substrate severely impedes the layout for the substrate-IC. In addition, more unit arrays on a chip means that the array efficiency becomes worse. To improve its integratibility, the 3D-M preferably uses large unit array(s).

Since it is equal to the product of N WL and N BL ( FIGS. 13B , 19 B), the unit-array capacity C A can be improved by increasing N WL and N BL . From a design perspective, N BL is not constrained and therefore, rectangular unit array can be used. On the other hand, from eq. (1) and letting ΔV be =nV T (in general, n˜2, V T ˜0.1V), N WL can be expressed, as,

N WL =I f ( V f )/ I r ( V r )= I f ( V R −V M −nV T )/ I r ( nV T )  eq. (3)

N WL is constrained by the rectification ratio γ of the 3D-ROM cell. Here, the γ definition is different from the conventional definition: the forward bias V f (e.g. 3V) can be far greater than the reverse bias V r (e.g. ˜0.3V). This attributes to the usage of S/A and other design improvements. Eq. (3) is very valuable to the unit-array design. Apparently, N WL can be increased by using large V R . Alternatively, polaried cells can be used to improve γ. In a polarized cell, the resistance a current faces when it flows in one direction is different from the resistance it faces when it flows in the other direction.

FIG. 19B illustrates a preferred rectangular 3D-M array. In this preferred embodiment, N BL >N WL . It is feasible to place a number of these arrays in a 3D-M chip along the y direction. Accordingly, the shape of the resulted final chip is approximately square.

FIG. 19 CA discloses an N WL -improving means based on large V R . Here, V R is larger than V dd . Since the IV characteristic of the 3D-ROM layer is exponential, the read current I 1 (at V R ) is far larger than the current I 2 (at V dd ). As a result, N WL and C A can increase significantly. FIGS. 19 CB- 19 CC illustrate a preferred V R -generating means. FIG. 19 CB is its circuit block diagram. V R -generating-block 12 R generates V R for the row decoder 12 . It is typically based on charge-pump design. FIG. 19 CC is a preferred substrate layout incorporating a V R -generating-block 12 R. The 3-D integration allows the V R -generating-block 12 R to be formed on the substrate 0 s , preferably under the 3D-M array 0 A.

Besides using a large V R , polarized cells can be used to increase C A . Polarized cell could comprise polarized layer and polarized structure. The polarized layer is based on the base-material difference (FIGS. 19 D- 19 EC); the polarized structure is based on the interface difference (FIGS. 19 F- 19 GC).

FIG. 19D explains the concept of polarized layer. A polarized layer 38 comprises at least two sub-layers 38 a , 38 b . Preferably, the materials forming these sub-layers 38 a , 38 b are substantially different. When a current flows through the polarized layer 38 along direction 37 a (i.e. from terminal 39 a to terminal 39 a ), it encounters the sub-layer 38 a first and the sub-layer 38 b next; on the other hand, when it flows along direction 37 b (i.e. from terminal 39 b to terminal 39 b ), the current encounters the sub-layer 38 b first and the sub-layer 38 a next. The sequence in which the current encounters the sub-layers 38 a , 38 b can strongly affect the magnitude of the current. One well-known example is p-n junction diode. By using opposite, dopant types in the sub-layers 38 a , 38 b , diode action can be observed. The polarized layer 38 goes further than diode: not only dopant types, but also the base materials are different in the sub-layers 38 a , 38 b . Here, base material is the major material component in a layer. FIGS. 19 EA- 19 EC illustrate several preferred polarized layers.

FIG. 19 EA illustrates a first preferred polarize 3D-ROM layer. It comprises two sub-layers 32 a , 32 b . They use different base materials. For example, the base material in the sub-layer 32 a is silicon and the base material in the sub-layer 32 b is silicon carbide (Si z C 1−z , 0≦z≦1). Other semiconductor materials, such as Si y Ge 1−y (0≦y≦1), C, are also base-material candidates. Besides semiconductor materials, the polarized layer 32 may comprise: composite layer of semiconductor and dielectric (e.g. sub-layer 32 a comprises a semiconductor material and sub-layer 32 b comprises a dielectric material), different dielectric materials (e.g. sub-layer 32 a comprises amorphous silicon and sub-layer 32 b comprises silicon nitride), base materials with different structures (e.g. sub-layer 32 a has an amorphous structure and sub-layer 32 b has a poly-crystalline or micro-crystalline structure. This is also illustrated in FIG. 19 EB), different electrode materials (e.g. metals of different work functions; or, metals with different interfacing properties with the 3D-ROM layer; or, one electrode uses metal, another electrode uses doped semiconductor). All these means can further improve the rectification ratio of the 3D-ROM cell.

FIG. 19 EB illustrates a second preferred polarized 3D-ROM layer. In this preferred embodiment, a micro-crystalline layer 32 au is inserted between the electrode 31 and the 3D-ROM layer 32 a . Its existence at one electrode interface (e.g. between the electrode 31 and the 3D-ROM layer 32 ) can polarize 3D-ROM layer 32 . In addition, the existence of micro-crystalline layer at at least one electrode interface (e.g. between the electrode 31 and the 3D-ROM layer 32 , and/or between the electrode 33 and the 3D-ROM layer 32 ) can lower the metal-semiconductor contact resistance, increase the forward current and therefore, reduce the latency.

FIG. 19 EC illustrates a third preferred polarized 3D-ROM layer. In this preferred embodiment, 3D-ROM layer 32 comprises a p+ layer 32 p , a ν layer 32 x and an n+ layer 32 n . The ν layer 32 x is lightly n doped or un-doped and all these layers are based on amorphous silicon (αSi). The layer-formation sequence is 32 n , 32 x , and 32 p . This preferred structure can achieve a forward current of >10 A/cm 2 and a reverse current <6×10 −5 A/cm 2 .

FIG. 19F explains the concept of polarized structure. The 3D-ROM layer 32 has a top interfaces 32 ti with the top electrode 33 and a bottom interface 32 bi with the bottom electrodes 33 . In a polaried structure, the shapes of these interfaces are different: one interface preferably has a field-enhancing tip 33 t , while the other interface is relatively smoother. Accordingly, electron emission can be enhanced along one direction and the rectification ratio can be improved.

FIG. 19G illustrates a preferred polaried structure. In this preferred embodiment, the bottom electrode 33 , being poly-crystalline, has a rough bottom interface 32 bi ; after the 3D-ROM layer 32 is deposited thereon, the amorphous material in the 3D-ROM layer 32 smoothes out the top interface 32 ti . As a result, electron emission from the bottom electrode 33 to the top electrode 31 can be enhanced. Namely, the current flowing from the top electrode 31 to the bottom electrode 33 can be larger than the other way around. Accordingly, the top electrode 31 can be used as word line and the bottom electrode 33 can be used as bit line.

5. Yield-Enhancement Techniques

Defects cause various read-out errors and are detrimental to yield. As illustrated in FIGS. 20 AA- 20 CB, there are six types of defects in a 3D-M array, including: 1. word-line open 20 o (FIG. 20 AA); 2. word-line short 20 s (FIG. 20 AB); 3. bit-line open 30 o (FIG. 20 BA); 4. bit-line short 30 s (FIG. 20 BB); 5. low 3D-ROM cell forward current (FIG. 20 CA); 6. large 3D-ROM cell reverse current (FIG. 20 CB).

For the word-line defects (types 1 and 2), no correct data can be read out for the entire word line. They cause word-line errors. For the bit-line defects (types 3 and 4), no correct data can be read out for the entire bit line. They cause bit-line errors. For the cell defect (type 5), the forward current 1 f ′ is too small. The resulted ΔV be might be too small to trigger the S/A and a logic “1” cell might be misread as logic “0” (FIG. 20 CA). Fortunately, this defect only causes single-bit error. For the cell defect (type 6), the defective 3D-ROM cell is leaky and its reverse current 1 r ′ is too large. When reading any other cells on the same bit line as the defective cell, the leakage current of the defective cell might limit ΔV be in such a way that the S/A cannot triggered and no valid data can be read out (FIG. 20 CB). This defect causes bit-line error. Defect types 5 and 6, particularly 6, are detrimental to the intrinsic yield of the 3D-M array.

To improve yield, the present invention discloses a seamless 3D-ROM cell. It reduces the number of defects in a 3D-ROM array (FIGS. 21 A- 23 B). Alternatively, error-correction schemes such as error-correction code (ECC) and redundancy circuit can be used (FIGS. 24 - 26 C). They can correct the errors caused by the defects in a 3D-M array.

A. Seamless 3D-ROM Cells

Defects can be introduced at several stages during the manufacturing process of the 3D-ROM, i.e. before the 3D-ROM layer formation (e.g. to the top surface of the bottom electrode), during the 3D-ROM layer formation (to the 3D-ROM layer), or after the 3D-ROM formation (e.g. to the top surface of the 3D-ROM layer). The cleanness of these layers (i.e. the 3D-ROM layer and the adjacent portions of top and bottom electrodes) has great impact to the intrinsic 3D-ROM yield. Accordingly, these layers are referred to as yield-sensitive layers. One common defect-introducing step is pattern transfer. During pattern transfer, wafers are subjected to lithography and etching (and/or planarizing). These steps can either introduce foreign particles or cause damage to the 3D-ROM layer. Thus, pattern transfer is preferably avoided during the formation of the yield-sensitive layers.

FIG. 21A illustrates a preferred seamless 3D-ROM cell. It can improve the intrinsic yield of the 3D-ROM array. This preferred seamless 3D-ROM cell comprises a bottom electrode 64 , a 3D-ROM layer 62 , and a top electrode 65 . The top electrode 65 further comprises a conductive top buffer layer 60 and a top conductor 65 , which are connected by via (opening) 67 . The interface between the top buffer layer 60 and the 3D-ROM layer 62 is the top interface 62 ti ; the interface between the 3D-ROM layer 62 and the bottom electrode 64 is the bottom interface 62 bi . During the 3D-ROM process (FIGS. 22 AA- 22 E′), the 3D-ROM layer and its adjacent layers are formed in a seamless way: there is no pattern transfer between these steps and therefore, no foreign particles are introduced to the top and bottom interfaces 62 ti , 62 bi . This process is preferably carried out in a cluster tool. FIG. 21B illustrates an alternate preferred 3D-ROM cell. In this preferred embodiment, nF-opening mask is used during the formation of the opening 67 . Accordingly, the dimension of the resulted opening 67 is larger than that of the top buffer layer 60 .

FIGS. 22 AA- 22 E′ illustrate several preferred process flows for the seamless preferred 3D-ROM cells. In FIG. 22 AA, all yield-sensitive layers, including the bottom electrode 64 , the 3D-ROM layer 62 and the top buffer layer 60 are formed in a seamless way. As a result, the amount of defects at the top and bottom interfaces 62 ti , 62 bi is minimized. Alternatively, an extra layer—an etchstop layer 60 b —is formed between the 3D-ROM layer 62 and the top buffer layer 60 (FIG. 22 AB). Its function will become apparent as FIG. 22 BC is explained. All these layers ( 64 , 62 , 60 b , 60 ) are also formed in a seamless way.

Then a pattern transfer step is performed to the top buffer layer 60 b . FIGS. 22 BA- 22 BC illustrate several preferred 3D-ROM structures after this step. In FIG. 22 BA, a portion of the bottom electrode 64 is exposed. In FIG. 22 BB, a portion of the 3D-ROM layer 62 is exposed. FIG. 22 BC is a resultant structure from FIG. 22 AB. The etchstop layer 60 b protects the 3D-ROM layer 62 from the etch of the top buffer layer 60 . In FIGS. 22 BA- 22 BB, at least a portion of the top electrode 66 (i.e. the top buffer layer 60 ) has the same cross-section as at least a portion of the 3D-ROM layer 62 .

After the top buffer layer 60 is defined, a repairing step is preferably performed to the edge of the 3D-ROM layer 62 (FIGS. 22 CA- 22 CC). This is similar to the post-gate-oxidation step in the conventional MOS process. FIG. 22 CA is a resultant structure from FIG. 22 BA. A portion of the bottom electrode 64 is converted into a dielectric 68 d by means such as oxidation. FIG. 22 CB is a resultant structure from FIG. 22 BB. A portion of the 3D-ROM layer 62 is converted into a dielectric 68 d by means such as oxidation. FIG. 22 CC is a resultant structure from FIG. 22 BC. A portion of the etchstop layer 60 b is converted into a dielectric 68 d by means such as oxidation.

Next, a pattern transfer step is performed on the bottom electrode 64 . This results in a 3D-ROM stack 69 (FIG. 22 D). Then a lower-level dielectric 68 is formed and a portion thereof is removed to form a via (opening) 67 . This is followed by the formation of the top conductor 65 (FIG. 22 E).

FIGS. 22 D′- 22 E′ illustrate the extra steps to form the preferred seamless 3D-ROM structure of FIG. 21 B. After the formation of the 3D-ROM stack 69 , a lower-level dielectric 68 is deposited and planarized. Then a config-dielectric 23 is formed thereon (FIG. 22 D′). The lower-level dielectric 68 and the config-dielectric 23 preferably comprise different dielectric materials, e.g. the lower-level dielectric 68 comprise silicon oxide and the config-dielectric 23 comprises silicon nitride. After being exposed to an nF-opening mask, the config-dielectric 23 is etched to form an opening 67 . The etch recipe is selected in such a way that this etch step stops on top of the lower-level dielectric 68 . Then the opening 67 is filled with conductive materials. After another pattern transfer, the top conductor 65 is formed (FIG. 22 E′).

FIGS. 23A-23B illustrate two preferred quasi-seamless 3D-EPROM cells. In these quasi-seamless cells, a portion of the 3D-EPROM layer (e.g. quasi-conduction layer 62 a ) is formed in a seamless way while the other portion (e.g. antifuse layer 62 b ) is formed in a conventional way. In FIG. 23A , the quasi-conduction layer 62 a is sandwiched between the top buffer layer 60 and the bottom electrode 64 . It is formed in a seamless way; on the other hand, the antifuse layer 62 b , sandwiched between the plug 63 and the top electrode 65 , is formed in a conventional way. In FIG. 23B , the quasi-conduction layer 62 a is formed in a seamless way; on the other hand, the antifuse layer 62 b , sandwiched between the top buffer layer 60 and the top electrode 65 , is formed in a conventional way. In these two preferred embodiments, the amount of defects in the quasi-conduction layer 62 a can be minimized. Note that the placements of the quasi-conduction layer 62 a and the antifuse layer 62 b can be switched.

B. Error-Correction Schemes

To improve the 3D-M yield, error-correction scheme can be used. It includes error-correction code (ECC) and redundancy circuit. FIG. 24 illustrates a preferred 3D-M incorporating ECC: It comprises a 3D-M core 0 incorporating ECC, a column decoder 70 and an ECC decoder 110 . In the 3D-ROM core 0 , each word line contains 1024 data bits. They are divided into 16 words of 64 bits. They can use Hamming code for error-correction. For Hamming code, each word of 64 bits requires 7 check bits. Thus, the total number of bits on each word line is (64+7)×16=1136. During read, these bits are supplied to the column decoder 70 . The output 79 a ′ from the column decoder 70 comprises 71 bits. The ECC decoder 110 converts these 71 bits 79 a ′ into a word 79 a with 64 valid bits.

Redundancy circuits can correct single-bit error, bit-line errors and word-line errors. FIG. 25A illustrates a first preferred 3D-M with redundancy circuits. It comprises a 3D-M core 0 , a column decoder 70 , three 64-bit 2-to-1 multiplexors 116 S, 116 B, 116 W and three redundancy blocks. The redundancy blocks include a single-bit redundancy block 118 S, a bit-line redundancy block 118 B and a word-line redundancy block 118 W. They correct single-bit errors, bit-line errors and word-line errors, respectively. Each redundancy block stores the addresses and correctional data for defects (e.g. defective cells, defective bit lines, defective word lines). When the input address matches a defect address, the correctional datum corresponding to this defect address is sent to a data input ( 117 S, 117 B, 117 W) of a multiplexor ( 116 S, 116 B, 116 W). Under the control of a selection signal ( 115 S, 115 B, 115 W), the correctional datum replaces the corresponding bit in the 3D-M output 79 ′″. The single-bit redundancy block 118 S and the bit-line redundancy block 118 B are illustrated in FIGS. 25B-25C ; since the word-line redundancy block 118 W can be used in software upgrade, it is illustrated in FIGS. 26B-26C .

FIG. 25B illustrates a single-bit redundancy block 118 S. This preferred embodiment comprises two correctional sets. They can correct two single-bit errors. Apparently, 118 S may include more correctional sets. Each correctional set comprises a number of registers. They store a valid bit vs 1 (1 bit), as well as the address and the correctional bit ds 1 (1 bit) for the defective cell. The stored defect address includes the upper 4 bits bs 1 of the column address, the row address ws 1 (10 bits) and the lower 6 bits bs 1 ′ of the column address. The selection port of each register is represented by “>”. The valid bit represents the validity of a correctional set: only when it is high, the correctional set is valid. The selection port 122 s of the valid-bit register is tied to V dd , or other timing signals (e.g. 74 r ). During read, comparator 121 a , 121 c compare the input column address 2 c , AS 2 with bs 1 , ws 1 , respectively. If they match, bs 1 ′, ds 1 are read out. Based on bs 1 ′, decoder 121 D raises the corresponding control line in 115 S to high. Meanwhile, ds 1 is sent to 117 S and under the control of 115 S, replaces the corresponding output 79 ″. Here, if the valid bit is low or the input address differs from the stored defect addresses, signal 122 D will be set to low and disable the decoder 121 D. This will drive all control lines in 115 S low and the multiplexor 116 S do not perform any data replacement.

FIG. 25C illustrates a bit-line redundancy block 118 B. This preferred embodiment comprises two correctional sets. They can correct two bit-line errors. Each correctional set stores a valid bit vb 1 (1 bit), as well as the address and the correctional column db 1 (1024 bits) for the defective bit lines. The stored defect address includes the upper 4 bits bb 1 of the column address and the lower 6 bits bb 1 ′ of the column address. The correctional column db 1 contains all correctional data for the defective bit line. During read, the column address 2 c is compared with bb 1 . If they match, bb 1 ′, db 1 are read out. Based on bb 1 ′, decoder 123 D raises the corresponding control line in 115 B to high. Meanwhile, a correctional bit is selected from db 1 based on AS 2 . It is sent to 117 B and replaces the corresponding output 79 a ′ under the control of 115 B.

The preferred redundancy circuits of FIGS. 25B-25C are based on “correct-during-read”. On the other hand, by taking advantage of the fact that the eRAM in a 3DiM keeps a copy of the 3D-M data, “correction-after-read” can be implemented. In “correction-after-read”, 3D-M data (including both correct data and erroneous data) are first copied into the eRAM, where they are to be corrected. FIG. 25 DA illustrates a preferred redundancy 118 SB based on “correction-after-read”. 118 SB first corrects single-bit errors, then it corrects bit-line errors. It comprises a single-bit correctional block 120 S and a bit-line correctional block 120 B. They correct single-bit errors and bit-line errors, respectively.

Single-bit correctional block 120 S comprises a first correctional storage block 126 S. It comprises a plurality of correctional sets. Each correctional set stores a valid bit 126 d (1 bit), as well as the address and the correctional bit for the defective cells. The stored defect address includes the column address bs (10 bits) and the row address ws (10 bits). In this preferred embodiment, all valid correctional sets are stored from the bottom of 126 S. When cRY 79 is set to high (i.e. data in the eRAM is ready), 126 S starts to read correctional sets one-by-one under the control a timing circuit 126 a . FIG. 25 DB, illustrates a preferred timing block 126 a . Its function is: as long as the valid bit 125 d is high, the timing block 126 a will keep sending out the clock signal 125 a for the counter 126 b ; once 125 d switches to low, it will send out the clear signal 125 b for the counter 126 b and single-bit-correction-done signal 79 ′. Accordingly, as long as valid correctional sets are being read out ( 125 d is high), the output 125 c of the counter 126 b keeps incrementing. This output 125 c is used as the address for the first correctional storage block 126 S. Address-decoder 126 c reads out a correctional set based on 125 c . Comparator 126 e compares ws 125 e with AS 2 . If they match, bs 125 f is sent to the address port A[9:0] of the eRAM 72 ; ds 125 g is sent to the data port D of the eRAM 72 and replaces the datum corresponding to the single-bit error.

Bit-line correctional block 120 B comprises a second correctional storage block 128 B. It comprises a plurality of correctional set. Each correctional set stores a valid bit 128 d (1 bit), as well as the column address bb (10 bits) and the correctional column db (1024 bits) for the defective bit lines. When the single-bit-correction-done signal 79 ′ is received, 128 B starts to read correctional sets. It uses the same timing circuit 128 a as 126 a . Similarly, when the valid bit 127 d is high, the counter 128 b will keep incrementing the address 127 c for 128 B. Address-decoder 128 c reads out bb 127 f based on 127 c and sends it to the address port A[9:0] of the eRAM 72 . Then 128 B selects a correctional bit 127 g (1 bit) from db based on AS 2 . This correctional bit 127 g is sent to the data port D of the eRAM 72 and replaces the datum corresponding to the bit-line error. The timing diagram for this preferred “correct-after-read” process is illustrated in FIG. 25 DC.

6. Software Upgradibility

During its lifetime, software is expected to experience a number of upgrades. During each upgrade, a portion of the original code (the initially released software code) is to be replaced by a upgrade code. It was generally believed that: if masked ROM (MROM) is used to store software, after the chip is shipped, the software stored therein cannot be upgraded. For a traditional MROM, this is true. For 3D-M, this belief is not valid. As explained before, the 3D-M carrying the original code can be easily integrated with a RWM (i.e. a 3DiM), which can be used to carry the upgrade code. Accordingly, the 3DiM supports software upgrade. Furthermore, because the upgrade code takes much less space than the original code, the RWM does not have to be large. This results in a low overall storage cost.

In order to facilitate software upgrade, software design is preferably based on a modular approach. FIG. 26 illustrates a preferred code storage in a 3D-M. Because the easiest data-replacing means is word-line replacement, i.e. all data on a single word line are replaced at the same time. Software modules stored in 3D-M array are preferred stored in units of 3D-M pages. In addition, they do not share 3D-M pages. Here, a 3D-M page (e.g. 20 S[0]) refers to all data stored on a word line (e.g. 20 [0]). In this preferred embodiment, software module 160 b contains 2047 bits; since each 3D-M page stores 1024 bits, 160 b is stored in two 3D-M pages 20 S[0], 20 S[1], among which the last bit 1 bz on page 20 S[1] is preferably a dummy. During an upgrade to the module 160 b , all data on the word lines 20 [0], 20 [1] are replaced by the upgrade code. This can be accomplished by flexible-code block.

FIGS. 26B-26C illustrate two preferred flexible-code blocks. These flexible-code blocks can also correct word-line errors. The first preferred flexible-code block of FIG. 26B is similar to FIGS. 25B-25C and is based on “upgrade-during-read”. It comprises two upgrade sets. They can upgrade two 3D-M pages. Each upgrade set stores a valid bit vw 1 (1 bit), as well as the row address ww 1 (10 bits) and the upgrade data dw 1 (1024 bits) for the page-to-be-upgraded. The selection port 161 s of the valid-bit register is preferably tied to cRD 75 . During read, comparator 162 a compares AS 2 and ww 1 . If they match, the upgrade codes 117 W (64 bits) are read from dw 1 based on 2 c . They replace the output data under the control of word-line-replacement signal 115 W. Accordingly, the external circuits only see the upgraded code. Alternatively, flexible-code block can also be based on “upgrade-after-read” (referring to FIG. 25 DA). Note that during a read cycle, if the data from a word line are to be replaced, there is no need to read data from the 3D-M and the 3D-M can be turned off Preferably the 3D-M is put into a “soft-off” mode (referring to FIG. 14 DD), thus saving power and supporting quick “wake-up” (i.e. put back into action).

The second preferred flexible-code block in FIG. 26C borrows the concept of page management in the virtual memory of a computer, i.e. it treats the input address as virtual address and performs an address-translation that convert it into physical address. This preferred flexible-code block comprises a 3D-ROM 0 , an upgrade block 86 O, an address decoder 164 D and an address-translation block 164 T. The 3D-ROM 0 stores the original code and the upgrade block 86 O, comprising RWM, stores the upgrade code. The 3D-M 0 and the upgrade block 86 O form a unified memory space 86 S. Here, the 3D-M 0 occupies the lower 1020 rows, i.e. R[00000 00000]-R[11111 11011], and the upgrade block 86 O occupies the upper 4 rows, i.e. R[11111 11100]-R[ 11111 11111 ]. The address-translation block 164 T stores the address or pseudo-address for the unified memory space 86 S. If pseudo-address is stored therein, the address-translation block 164 T preferably comprises a processing block, which converts the pseudo-address to physical address. The input address 86 A of the address-translation block 164 T is the upper 10 bits of the input address A[13:4]. Its output 86 TA contains 10 bits TA[9:0], which is eventually sent to the address-decoder 164 D and used as the physical address for 86 S. The address-decoder 164 D performs address-decoding for 86 S based on the physical address. When the original code is needed, the physical address points to the 3D-M 0 . For example, if 86 A is 00000 00000 (i.e. row 165 a of 164 T), the corresponding 86 TA is 00000 0000, which points to row R[00000 00000] of the 3D-M 0 , i.e. the original code. When the upgrade code is needed, the physical address points to the upgrade block 86 O. For example, if 86 A is 00000 00100 (i.e. row 165 d in 164 T), the corresponding 86 TA is 11111 11110, which points to row R[11111 11110] of the upgrade block 86 O, i.e. the upgrade code. Address-translation can be easily applied to software upgrade, correction of word-line errors, and ConC (referring to FIG. 3 D).

7. 3D-M-Based Self-Test (3DMST)

In the “design-for-test (DFT)” adopted by the conventional IC design, a plurality of muxed-flip-flops (mux-FF) are connected into at least one scan chain. During test, input test vectors (ITV) are shifted into the scan chain. Then the output from the circuit-under-test (CUT), i.e. output test vectors (OTV), are shifted out of the scan chain and compared with the expected test vectors (ETV) from the tester. If all OTV and ETV match, the CUT passes this test.

FIG. 27A is an exemplar CUT 0 cut before DFT. It comprises three pipelined stages S 1 -S 3 . Each stage (S 1 ) comprises a plurality of flip-flops ( 01 f , 02 f ) and a logic network ( 1 N). The output of the logic network 1 N at the first stage S 1 is the input X 3 of the flip-flop 03 f at the second stage S 2 . The circuit in FIG. 27A is used throughout this disclosure as the CUT.

FIG. 27B illustrates a conventional DFT-based CUT. It replaces every flip-flop ( 01 f - 04 f ) in FIG. 27A with a mux-FF ( 01 sf - 04 sf ). For the reason of simplicity, all logic networks 1 N, 2 N in FIG. 27A are combined into a single network 12 N. The inputs D, SI in the mux-FF is controlled by a scan-enable (SE) signal: when SE is low, the flip-flop in the mux-FF uses the normal input D; otherwise, it uses the scan input SI. Here, mux-FF's 01 sf - 04 sf are connected one-by-one and form a scan chain 0 sfc . ITV 002 is fed in from the input port SI 00 si and OTV 006 is sent out to the output port SO 00 so . In this preferred embodiment, the ITV width is 3 and the OTV width is 2.

A. 3DMST Concept

For the conventional testing methodology, it is difficult to perform at-speed test to high-speed circuits. Moreover, the testers are costly and do not support field-test and field-diagnosis. With the advent of 3D-M, particularly 3D-ROM, the industry acquires a storage device with large capacity and low cost. It is an ideal carrier for test vectors (e.g. ITV and ETV). More importantly, 3D-M is highly integratible, i.e. 3D-M can be easily integrated on top of the CUT. In fact, the integrated 3D-M and CUT is a form of 3DiM (referring to FIG. 2 A). This integration causes minimum impact to the CUT layout (referring to FIG. 2 B). Moreover, data flow between the 3D-M and the CUT is large (i.e. has a large bandwidth, referring to FIG. 17 ). Thus, at-speed test can be easily carried out. Apparently, 3D-M supports field self-test. Accordingly, this testing methodology is referred to as 3D-M-based self-test (3DMST).

In fact, the 3D-M array does not have to cover the whole CUT chip. It is acceptable for the 3D-M array to cover a fraction of the chip. If the CUT contains an area where, no routing is required for two adjacent interconnect layers, then this area can be used to form a 3D-M array. Accordingly, the introduction of a 3D-M array to a CUT may not require building extra interconnect layers. On the other hand, 3D-M does not need to be active during the normal operation of the CUT; it only needs to be activated during test. During the normal operation of the CUT, the state-control signal 6 E (referring to FIG. 14 DD) is preferably asserted. This forces the 3D-M into the “soft-off” mode and saves power.

FIG. 28A is a block diagram of a preferred integrated circuit supporting 3DMST (3DMST-IC) and FIG. 28B illustrates a preferred test flow. The 3DMST-IC comprises a CUT 0 cut, a 3D-M 0 and a test-vector buffer (TVB) 206 . The 3D-M 0 carries the test vectors for the CUT (e.g. ITV and ETV). The TVB 206 comprises an ITV buffer 202 and an ETV buffer 208 . The test vectors 206 td in the 3D-M 0 are first downloaded into the TVB 206 . This includes steps of downloading the ITV 002 into the ITV buffer 202 (step 222 ) and downloading the ETV 008 into the ETV buffer 208 (step 224 ). Next, the CUT 0 cut processes the ITV 002 and generates the OTV 006 (step 223 ). Then comparator 210 compares the OTV 006 with the ETV 008 . If they match (step 226 ), or, in the case of mismatch, if further diagnosis or secondary test are needed (step 225 ), a new 3D-M address is generated and the steps 222 - 226 are repeated until the 3DMST is done (step 227 ); under other circumstances, the CUT is considered failing this test (step 228 ).

FIG. 28C discloses more details on a preferred arrangement of a test-vector-carrying 3D-ROM array 0 A and its TVB 206 . They are the hardware implementation for the steps 222 , 224 of FIGS. 28A-28B . The 3D-ROM array 0 A comprises a plurality of word/bit lines ( 20 a , 30 b ) and diodes representing test data ( 1 ab - 1 aj ). In this preferred embodiment, each word line ( 20 a ) carries two test vectors ( 006 , 006 ′). Each test vector contains 5 bits of test data, including 3 bits of ITV and 2 bits of ETV. Based on row address 2 and column address 2 c , the test vector 006 is transferred into the TVB 206 . Inside the TVB 206 , flip-flops 1 f 1 - 1 f 3 form ITV buffer 202 and 1 f 4 - 1 f 5 form ETV buffer 208 .

Since the 3D-M 0 is integrated with the TVB 206 in a 3-D fashion, test vectors can be transferred from the 3D-M 0 to the TVB 206 in parallel through a large number of contact vias. This results in a large bandwidth. Moreover, the flip-flops 1 f 1 - 1 f 5 in the TVB 206 are fast. Accordingly, the 3DMST-IC supports at-speed (i.e. high-speed) test. In FIG. 28C , test vectors are directly transferred to the TVB 206 through the column decoder 70 . Alternatively, test vectors can be buffered into an eRAM first, before they are transferred from the eRAM to the TVB 206 (referring to FIG. 17 ).

FIGS. 29 AA- 29 BC disclose two test-vector downloading means: one is serial downloading (FIGS. 29 AA- 29 AD), i.e. test vectors are shifted into scan flip-flops one-by-one; the other is parallel downloading (FIGS. 29 BA- 29 BC), i.e. test vectors are shifted into scan flip-flops in parallel.

FIG. 29 AA is a preferred serial test flip-flop (SL-TFF). Its design is same as that the muxed-FF in FIG. 27 B. FIG. 29 AB is a preferred serial-load 3DMST-IC (SL-3DMST-IC). Compared with FIG. 27B , the input SI 00 si to the first SL-TFF 01 sf is the ITV 002 from the ITV buffer 202 ; the output SO 00 so from the last SL-TFF 04 sf is compared with the ETV 008 from the ETV buffer 208 ; and the comparison result CO 00 co is sent to a back-end screening circuit 00 pp , which determines if the CUT passes this test. The ITV buffer 202 and the ETV buffer 208 comprise parallel-in-serial-out modules (PISO). Their outputs 202 i , 208 o are driven by clock signals CKI 202 c , CKO 208 c , respectively; their inputs 202 td , 208 td are controlled by the parallel input-control signals PEI 202 p , PEO 208 p , respectively. At the beginning of the 3DMST, a clearing signal 00 cl clears the counter 00 ctr . Then, at the arrival of each clock signal CKT 00 ct , the counter 00 ctr increments the 3D-M address 2 .

FIG. 29 AC is a timing diagram for the preferred SL-3DMST. In this preferred embodiment, CK, CKI, CKO share one clock source, PEI, PEO share another clock source. During clock cycles T 1 -T 3 , serial-load control signal SE 00 s is high and the nth ITV(n) is shifted into SL-TFF 01 sf - 03 sf one-by-one. During clock cycle T 4 , SE 00 s switches to low and SL-TFF 03 sf - 04 sf acquire normal inputs X 3 , X 4 , which are the processing results of ITV(n) in the network 12 N, i.e. OTV(n). During clock cycles T 5 -T 6 , OTV(n) are shifted out and compared with the ETV 208 o . Since the OTV width is 2, the comparison result CO 00 co are valid only during the clock cycles T 5 -T 6 . Accordingly, T 5 -T 6 are referred to as valid OTV clock cycles. Here, input, processing and output need 4 clock cycles, which form a serial test cycle (STC). Note that the ETV(n) corresponding to the ITV(n) in a first STC are read out during the following STC.

FIG. 29 AD illustrates a preferred back-end screening circuit 00 pp . In this preferred embodiment, as long as OTV mismatches with ETV (i.e. 00 co is “1”) during any valid OTV clock cycle, the output P/F 00 pf of the back-end screening circuit 00 pp is latched to “1”. This preferred embodiment further comprises a register 208 pn , a counter 208 ctr and a comparator 208 lt . They determine if the comparison result obtained during a clock cycle is valid. Here, the register 208 pn stores the OTV width; the counter 208 ctr records the number of clock cycles elapsed after the beginning of each STC; and the comparator 208 lt compares these two numbers. If the number of clock cycles is smaller than the OTV width, the comparison result is valid.

FIGS. 29 BA- 29 BB illustrate two preferred parallel self-test flip-flops (PL-TFF). The PL-TFF 01 pf has an expected-value input ER and a comparison-result output CO. The data from ER is compared with the data from the output Y of the flip-flop and the comparison result is sent out at CO. Data-selection port PE determines if flip-flop 0 f captures normal input D or test data PI from the 3D-M. FIG. 29 BB has an extra switch 00 sw . During normal operation, 00 sw cuts comparator 00 xo from the CUT; 00 sw is switched on only during test.

FIG. 29 BC illustrates a preferred parallel-load 3DMST-IC (PL-3DMST-IC). Here, TVB 206 is a simple buffer. Its input is controlled by an input-control clock CKP′ and their outputs are driven by an output-control signal CKP. The test vectors ( 202 a - 202 c , 208 a - 208 b ) in the TVB 206 are fed into the PL-TFF 01 pf - 04 pf in parallel. Since PL-TFF 01 pf - 02 pf belong to the first stage S 1 where no data are processed (referring to FIG. 27 A), they do not have expected values. Accordingly, only the comparison results 00 co from PL-TFF 03 pf - 04 pf need to be sent to the back-end screening circuit.

The operation of a PL-3DMST-IC can be explained with the help of the timing diagram of FIG. 29 BD. Under the control of CKP, at time tx, the test vector 206 td from the 3D-M 0 is fed into the TVB 206 . During clock cycle Ta, the parallel-input control signal PE is set to high and the test vector 206 td is transferred into the PL-TFF 01 pf - 04 pf in parallel. Then the CUT processes the ITV and generates the OTV. During clock cycle Th, PE is set to low. At this moment, the OTV from a first stage is captured by the PL-TFF in the following stage and evaluated. Accordingly, each parallel self-test cycle (PTC) comprises 2 clock cycles.

B. 3DMST Applications

In real circuit applications, 3DMST can support parallel self-test (FIG. 30 A), mixed-signal testing (FIGS. 30 BA- 30 BC), printed-circuit board (PCB) system self-test (FIG. 30 C).

Most integrated circuits comprise a number of scan chains. FIG. 30A illustrates a preferred 3DMST-IC supporting parallel self-test. In this preferred embodiment, test vectors 206 tda , 206 tdb are downloaded from the 3D-M 0 to the ITV 206 a , 206 b , respectively. This downloading process is carried out in parallel. Accordingly, two CUT's 0 cuta, 0 cutb can be tested in parallel. This shortens testing time.

Mixed-signal circuit contains analog signals. Since digital-to-analog (D/A) conversion is much faster than the other way around, during the mixed-signal testing, ITV and/or ETV are preferably converted into analog signals when necessary. FIG. 30 BA illustrates a preferred 3DMST-IC supporting mixed-signal testing. In this preferred embodiment, the input of the CUT 0 cutm includes analog signals and its output 006 are purely digital. The ITV 002 d is converted into an analog signal by an on-chip analog-signal generating block 0 sg , before it is sent to the CUT 0 cutm. FIG. 30 BB illustrates a preferred analog-signal generating block 0 sg . It comprises a D/A converter 0 dac and a mixer 0 sm . The D/A converter 0 dac converts the ITV 002 d into an analog signal 002 a ′. The mixer 0 sm mixes this analog signal 002 a ′ with a carrier wave 002 cw and generates a test signal 002 a . On the other hand, the 0 cutm output in FIG. 30 BC includes output analog signal 006 . The ETV 008 are converted into expected analog signal 008 a by a D/A converter 0 dac ′. The expected analog signal is compared with the output analog signal 006 at an analog comparator 210 a to obtain the comparison result 00 co . The analog comparator 210 a may comprise a differential amplifier such as 17 C and an integrator.

FIG. 30C illustrates a preferred 3DMST-IC supporting printed-circuit board PCB) system self-test. The PCB 268 comprises a 3DMST-IC chip 262 and other conventional IC chips 264 , 266 . The 3D-M in the 3DMST-IC 262 carries test vectors not only for the 3DMST-IC 262 , but also for the conventional IC 264 , 266 . Accordingly, the 3DMST-IC 262 supports the self-test for the whole PCB system 268 . Moreover, since the 3D-M has a large capacity, this test will have good fault coverage.

In the preferred embodiment of FIG. 30C , the first interface 269 is the standard interface between the PCB system 268 and the external system; the second interface 261 can be used to perform a separate test to the 3DMST-IC 262 . The purpose of this separate test is to guarantee that the 3D-M in the 3DMST-IC 262 is error-free. It is a memory test and can be carried out by medium-to low-speed testers. Once the 3DMST-IC 262 passes this test, the PCB system self-test can be carried out at high speed and confidently.

C. Test Data Reduction

In order to reduce the amount of test data to be carried by a 3D-M, test-data compression can be used (FIGS. 31 AA- 31 AB): Alternatively, composite test can be used (FIGS. 31 BA- 31 BB).

FIG. 31 AA illustrates a preferred 3DMST-IC based on compressed test data Compared with FIG. 28A , the input of this preferred CUT further comprises an input-data de-compression circuit 0 dc and the output further comprises an output-data compression circuit 0 cp . The 3D-M 0 carries the ITV seeds 002 c , which are converted into the ITV 002 by the input-data de-compression circuit 0 dc . The processing results 006 are compressed by the output-data compression circuit 0 cp before they are compared with the ETV 008 .

FIG. 31 AB illustrates a preferred input-data de-compression circuit 0 dc . It is an LFSR-generating-block 0 dc . Before test, the control signal SL 0 sl is asserted and the ITV seeds 002 c are shifted into the flip-flops 01 if - 03 if . During test, SL 0 sl is de-asserted and the LFSR-generating-block 0 dc generates a series of pseudo-random numbers. The output-data compression circuit 0 cp can be a signature analyzer. This should be apparent to those skilled in the art. Alternatively, IC-testing may use only one of the above (de-) compression circuits.

FIGS. 31 BA- 31 BB explain two composite tests. Composite test combines at least two testing methods, e.g. 3DMST, built-in-self-test (BIST) and external scan test (EST). It exploits the individual strength of each testing method. As illustrated in FIG. 31 BA, basic circuit blocks (e.g. RAM) can use the BIST, while the higher-level testing (e.g. chip-level functional/structural testing) can use the 3DMST. On the other hand, as illustrated in FIG. 31 BB, the high-speed test can be relied on the 3DMST and/or BIST, while the medium- to low-speed test can be based on the EST. This can lower the overall testing cost. Alternatively, critical test vectors (i.e. the test vectors important to the circuit performance) are tested by the 3DMST, while the non-critical test vectors are tested by the EST. This improves the chance of locating defects during the field-test. Composite test can optimize the testing cost and reliability.

D. Methodologies to Avoid Undesired Yield Loss

During the 3DMST, if the OTV mismatches with the ETV, there are two possibilities: one is the CUT is defective; the other is the 3D-M is defective. The second scenario causes undesired yield loss. To avoid this, 3DMST-with-confidence may be used, i.e. 3D-M is guaranteed to be error-free, and if there are any defect-induced errors, they are corrected before the 3DMST (FIG. 32 ). Alternatively, secondary test can be used, i.e. after the 3DMST, a conventional EST is performed on the chips that fail the 3DMST (FIGS. 33 A- 33 D).

FIG. 32 illustrates a preferred flow for the 3DMST-with-confidence. During the 3DMST-with-confidence, the 3D-M 0 carrying the test vectors needs to be error-free. Accordingly, before the 3DMST, the 3D-M 0 is tested (step 231 ). This testing step can be performed in a medium- to low-speed tester and therefore, is a low-cost testing step. If the 3D-M 0 does not pass the test, the 3D-M errors are to be corrected by various correctional means (step 234 , referring to FIGS. 25 A- 26 C). For the CUT whose 3D-M 0 cannot be corrected, it has to go through the EST (step 236 ) and/or dual testing (step 237 , referring to FIG. 33 ).

FIGS. 33 A- 33 CB illustrates several preferred integrated circuit with dual-testing capability (DTC-IC). Besides supporting the 3DMST, the DTC-IC also supports the EST. As illustrated in FIG. 33A , during dual testing, a secondary test is performed to the CUT, i.e. after the 3DMST, a conventional EST is performed to the chip that fail the 3DMST (step 230 ). If said chip still fails the EST, it is considered a bad part. To reduce the EST test time during the dual testing, the questionable test vectors 004 (QTV, i.e. the ITV corresponding to mismatched OTV and ETV) are preferably recorded during the 3DMST (step 229 ). During the EST, testing is only performed to the QTV 004 (step 229 C).

FIG. 33 BA illustrates a preferred SL-3DMST-IC with DTC. It adds two multiplexors 00 m 1 , 00 m 2 at each end of the SL-TFF chain 00 sfc . The multiplexor 00 m 1 determines if the ITV fed into the SL-TFF chain 00 sfc is the ITV 202 i from the 3D-M 0 or the test data ESI 00 esi from the external tester. On the other hand, the multiplexor 00 m 2 determines if the output 00 eo from the SL-TFF chain 00 sfc is the comparison result CO 00 co or the OTV SO 00 so.

FIG. 33 BB is a preferred back-end screening circuit 00 pp ′. Compared FIG. 29 AD, it has a QTV storage block 204 . The QTV storage block 204 comprises a number of QTV-address registers 204 a - 204 d and comparison-result registers 204 af - 204 df . The QTV address 2 QA may include the 3D-M address 2 and the location 208 n of the questionable bit in the OTV. Here, questionable bit is the bit in the OTV that does not match with that in the ETV. It helps to diagnose the defective CUT. If a valid comparison result CO 00 co is high, 204 af is set to high, 2 QA is fed into the first QTV register 204 a and the earlier 2 QA's are shifted one register to the right. As long as the output 00 pf is high, the CUT fails the 3DMST.

FIGS. 33 CA illustrate a preferred PL-3DMST-IC with DTC. It replaces all PL-TFF 01 pf - 04 pf in FIG. 29 BC by parallel-serial test flip-flops (PS-TFF) 01 df - 04 df . These PS-TFF 01 df - 04 df form a PS-TFF chain 00 dfc . Under the control signal DE[0:1] 00 de , each PS-TFF captures one signal from the following inputs: the normal input D, the ITV downloaded in series from an external tester, or the ITV downloaded in parallel from the 3D-M 0 . A preferred PS-TFF is illustrated in FIG. 33 CB. Its operation should be apparent to those skilled in the art.

It should be noted that, although various types of the 3D-M (including both EP-3DM and NEP-3DM) have been described in the Specification, the scope of this Application is limited to the EP-3DM only. The NEP-3DM is expressly excluded from the scope of this Application.

While illustrative embodiments have been shown and described, it would be apparent to those skilled in the art that may more modifications than that have been mentioned above are possible without departing from the inventive concepts set forth therein. For example, the 3D-M array in this disclosure is typically 1024×1024. In fact, its size in real application could be as large as ˜10 4 ×10 4 . On the other hand, the 3DMST-IC in this disclosure is based on mux-FF. In fact, they could be based on LSSD and other DFT designs. The invention, therefore, is not to be limited except in the spirit of the appended claims.

Claims

1. An integrated circuit (IC) supporting electrically programmable three-dimensionalmemory (EP-3DM)-based self-test (EP-3DMST), comprising: a substrate circuit, said substrate circuit further comprising a circuit-under-test (CUT) and a peripheral circuit; and, at least an EP-3DM level stacked on said substrate circuit, at least a portion of said EP-3DM level storing at least a portion of a form of test data for said CUT and being connected with said peripheral circuit through a plurality of inter-level connecting vias.

2. The IC supporting EP-3DMST according to claim 1, wherein said form of test data is a form of input test vectors (ITV).

3. The IC supporting EP-3DMST according to claim 2, wherein said form of ITV is ITV.

4. The IC supporting EP-3DMST according to claim 2, wherein said form of ITV is a source of said ITV.

5. The IC supporting EP-3DMST according to claim 4, wherein said source of said ITV is ITV seeds.

6. The IC supporting EP-3DMST according to claim 1, wherein said form of test data is a form of expected test vectors (ETV).

7. The IC supporting EP-3DMST according to claim 6, wherein said form of ETV is ETV.

8. The IC supporting EP-3DMST according to claim 6, wherein said form of ETV is a compressed ETV.

9. The IC supporting EP-3DMST according to claim 1, wherein said substrate circuit further comprises a plurality of test-vector buffers, said test-vector buffers storing at least a portion of said form of test data.

10. The IC supporting EP-3DMST according to claim 1, wherein said form of test data is downloaded into said CUT in a serial fashion.

11. The IC supporting EP-3DMST according to claim 1, wherein said form of test data is downloaded into said CUT in a parallel fashion.

12. The IC supporting EP-3DMST according to claim 1, wherein:said CUT comprises a first CUT block and a second CUT block; said substrate circuit further comprises a first test-vector buffer and a second test-vector buffer, said first test-vector buffer storing at least a portion of a form of test data for said first CUT block, said second test-vector buffer storing at least a portion of a form of test data for said second CUT block.

13. The IC supporting EP-3DMST according to claim 1, wherein said substrate circuit further comprises a D/A converter, said D/A converter converting at least a portion of said form of test data from digital into analog signals.

14. The IC supporting EP-3DMST according to claim 13, wherein said substrate circuit further comprises an analog comparator.

15. The IC supporting EP-3DMST according to claim 5, wherein said substrate circuit further comprises a data de-compressor for said ITV seeds.

16. The IC supporting EP-3DMST according to claim 6, wherein said substrate circuit further comprises a data comparator, said data comparator comparing said form of ETV for said CUT with a form of output test vectors (OTV) from said CUT.

17. The IC supporting EP-3DMST according to claim 8, wherein said substrate circuit further comprises a data compressor, said data compressor compressing OTV from said CUT.

18. The IC supporting EP-3DMST according to claim 1, wherein said substrate circuit further comprises a storage block, said storage block storing address information associated with mismatched OTV and ETV.

19. The IC supporting EP-3DMST according to claim 1, wherein said substrate circuit further comprises a multiplexor, the output of said multiplexor being selected from an external scan-test input, or from said EP-3DM.

20. The IC supporting EP-3DMST according to claim 1, wherein said substrate circuit further comprises a plurality of parallel-serial test flip-flops (PS-TFF), the output of said PS-TFF being selected from a normal data input, or from an external scan-test input, or from said EP-3DM.